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| United States Patent |
5,610,504
|
|
Tsugita
|
March 11, 1997
|
Automatic regulating circuit for regulating target signal through binary
search
Abstract
An automatic regulating circuit gradually regulates an output voltage to a
reference value in synchronism with a clock signal, and has a binary
search controller changing the value of a control signal across a final
value corresponding to said reference value until a convergence at the
final value; the control signal is supplied to a level shifting system so
as to converge the output voltage at the reference value, and the
automatic regulating circuit quickly completes the voltage regulation.
| Inventors:
|
Tsugita; Masami (Tokyo, JP)
|
| Assignee:
|
NEC Corporation (Tokyo, JP)
|
| Appl. No.:
|
526209 |
| Filed:
|
September 11, 1995 |
Foreign Application Priority Data
| Current U.S. Class: |
323/283; 323/281 |
| Intern'l Class: |
G05F 001/445 |
| Field of Search: |
323/274,280,281,282,283,284
|
References Cited
U.S. Patent Documents
| 3818306 | Jun., 1974 | Marini | 323/283.
|
| 4438498 | Mar., 1984 | Sekel et al. | 323/283.
|
| 5432693 | Jul., 1995 | Anderson | 323/283.
|
Other References
T. Tamura et al.; "A Single-Chip Video-Processing IC Made by an Improved
BI-CMOS Process"; 1992 IEEE WPN 15.7, pp. 264-265.
|
Primary Examiner: Wong; Peter S.
Assistant Examiner: Han; Y. J.
Attorney, Agent or Firm: Whitham, Curtis, Whitham & McGinn
Claims
What is claimed is:
1. An automatic regulating circuit for regulating an output signal to a
reference value, comprising:
a comparator having a first input node supplied with said reference value
and a second input node supplied with said output signal, and generating a
comparative signal indicative of either higher or lower than said
reference value;
a binary searching unit responsive to said comparative signal so as to
change the value of a control signal in such a manner as to converge
toward a target value corresponding to said reference value in synchronism
with a clock signal,
said binary search unit determining the value of said control signal at nth
clock pulse of said clock signal to be an intermediate value between the
value of said control signal at (n-1)th clock pulse of said clock signal
and the value of said control signal at (n-2)th clock pulse of said clock
signal when said comparator changes the comparative signal between a first
state indicating said output signal higher than said reference value and a
second state indicating said output signal lower than said reference
value,
said binary search unit determining the value of said control signal at
said nth clock pulse of said clock signal in the present of said
comparative signal indicating one of said first state and said second
state to be an intermediate value between the value of said control signal
at said (n-1) clock pulse of said clock signal in the presence of said
comparative signal indicating the other of said first state and said
second state and the latest value of said control signal in the presence
of said comparative signal indicating said one of said first state and
said second state; and
a shifting unit responsive to said control signal so as to change said
output signal.
2. The automatic regulating circuit as set forth in claim 1, in which said
binary searching unit includes
a register having a plurality of stages for storing said control signal,
and setting said control signal to an initial value between a maximum
value thereof and a minimum value thereof in synchronism with a first
clock pulse of said clock signal, said register changing the value of said
control signal in synchronism with each of second to said nth clock
pulses,
a shift register storing a first signal having two bits of a first logic
level in synchronism with said first clock pulse, and shifting said two
bits from the most significant bit toward the least significant bit in
synchronism with each of said second to said nth clock pulses, and
a switching circuit having a plurality of stages respectively associated
with said plurality of stages of said register, each of said plurality of
stages of said switching circuit having first input nodes supplied with
said two bits, a second input node supplied with a bit of said control
signal from the associated stage of said register, a third input node
supplied with said comparative signal and an output node coupled to an
input node of said associated stage of said register.
3. The automatic regulating circuit as set forth in claim 2, in which each
of said stages of said switching circuit includes
a NAND gate having fourth input nodes respectively coupled to one of said
first input nodes and said third input node,
a first AND gate having a fifth input node coupled to an output node of
said NAND gate and a sixth input node coupled to the other of said first
input nodes,
an inverter having a seventh input node coupled to said other of said first
input nodes,
a second AND gate having eighth input nodes respectively coupled to an
output node of said inverter and said second input node, and
an OR gate having ninth input nodes respectively coupled to an output node
of said first AND gate and an output node of said second AND gate.
4. The automatic regulating circuit as set forth in claim 2, in which said
switching circuit supplies a second signal to said register, and said
first signal and said control signal cause said switching circuit to
change two bits of said second signal to one of a first bit pattern and a
second bit pattern depending upon said comparative signal,
said two bits of said second signal being the most significant bit and a
first intermediate bit next to said most significant bit at said second
clock pulse,
said two bits of said second signal being sequentially shifted toward the
least significant bit of said second signal by one bit in response to said
clock signal.
5. The automatic regulating circuit as set forth in claim 4, in which said
two bits takes said first bit pattern in the presence of said comparative
signal indicative of said target signal smaller than said reference value
and second bit patter in the presence of said comparative signal
indicative of said target signal larger than said reference value, said
two bits in said first bit pattern being larger in value than said two
bits in said second bit pattern.
6. The automatic regulating circuit as set forth in claim 1, in which said
binary search unit includes
a binary search controlling unit responsive to said comparative signal so
as to change the value of a digital control signal in such a manner as to
converge toward said target value corresponding to said reference value in
synchronism with said clock signal, and
a digital-to-analog converter for converting said digital control signal to
an analog control signal.
7. The automatic regulating circuit as set forth in claim 6, in which said
shifting unit includes
a level shifter responsive to said analog control signal so as to produce a
level-shifted signal from a potential level of an input signal,
a transistor responsive to said level-shifted signal so as to change the
amount of current passing therethrough, and
a current-to-voltage converting means for converting said current to said
output signal.
8. The automatic regulating circuit as set forth in claim 6, in which said
shifting unit includes
a phase shifter for producing a phase-shifted signal from an input signal,
a band-pass filter responsive to said analog control signal for changing a
center frequency, and producing a regulated signal, and
a multiplier operative to multiply said regulated signal by said
phase-shift signal for producing said output signal.
Description
FIELD OF THE INVENTION
This invention relates to an automatic regulating circuit improved in
response characteristics and, more particularly, to an automatic
regulating circuit quickly regulating a target signal through a binary
search.
DESCRIPTION OF THE RELATED ART
A typical example of the automatic regulating circuit is disclosed by T.
Tamura et. al. in "A SINGLE-CHIP VIDEOPROCESSING IC MADE BY AN IMPROVED
BI-CMOS PROCESS", 1992 IEEE WPN 15.7, pages 264 and 265, and the prior art
automatic regulating circuit is illustrated in FIG. 1 of the drawings.
A comparator 1, an up-and-down counter 2, a digital-to-analog converter 3
and a level-shifter 4 form in combination the prior art automatic
regulating circuit, and the level shifter 4 is incorporated in an output
circuit for driving a cathode ray tube 7 in cooperation with a bipolar
transistor 8.
A reference voltage source 9 supplies a reference voltage REF to the
comparator 1, and the comparator compares the collector voltage Vc with
the reference voltage REF. The comparator 1 increments or decrements the
up-and-down counter 2 depending upon the potential difference between the
collector voltage Vc and the reference voltage REF. The up-and-down
counter 2 is responsive to a clock signal for changing the value of an
eight-bit digital output signal. Namely, when the comparator 1 instructs
an increase/decrement of the digital value represented by the eight-bit
digital output signal of the up-and-down counter 2, the up-and-down
counter 2 repeats the increment/decrement of the digital value in response
to the clock signal, and the increment/decrement at every clock pulse is
"1".
The eight-bit digital output signal is supplied from the up-and-down
counter 2 to the digital-to-analog converter 3, and the digital-to-analog
converter 3 generates an analog control signal ALG corresponding to the
eight-bit digital output signal. The analog control signal ALG is supplied
to the level shifter 4, and the level shifter 4 shifts an RGB signal by
the potential level represented by the analog control signal ALG.
The RGB signal regulated by the level shifter 4 is supplied to the base
node of the bipolar transistor 8, and the bipolar transistor 8 drives the
load or the cathode ray tube 7. The driving current is fed back to the
comparator 1 as the collector voltage Vc, and the prior art automatic
regulating circuit controls the RGB signal in such a manner as to match
the collector voltage Vc to the reference voltage REF.
The prior art automatic regulating circuit counters a problem in the
response time. The up-and-down counter 2 increments and decrements the
eight-bit digital signal by "1" at every clock pulse. The prior art
automatic regulating circuit completes the regulation within several clock
pulses in so far as the potential difference between the collector voltage
Vc and the reference voltage REF is small. However, if the potential
difference is large, a substantial amount of time is consumed by the prior
art automatic regulating circuit. For example, if the eight-bit digital
signal is indicative of a neutral value, i.e., the mid point of 256 values
and the target digital value is the maximum or the minimum of the
eight-bit digital signal, the up-and-down counter 2 is expected to repeat
the increment/decrement 128 times, and consumes 128 clock pulses.
Even though most of the regulation is completed within 10 clock pulses, the
maximum time period corresponding to 128 clock pulses is shared to every
regulation. If another signal processing follows the automatic regulation,
the signal processing circuit is expected to quickly complete the given
task, and the signal processing sequence becomes so tight.
SUMMARY OF THE INVENTION
It is therefore an important object of the present invention to provide an
automatic regulating circuit which quickly regulates an actual level to a
target level.
To accomplish the object, the present invention proposes to change a
control signal in such a manner as to converge toward a target value
corresponding to a reference level.
In accordance with the present invention, there is provided an automatic
regulating circuit for regulating an output signal to a reference value,
comprising: a comparator having a first input node supplied with the
reference value and a second input node supplied with the output signal,
and generating a comparative signal indicative of either higher or lower
than the reference value; a binary searching unit responsive to the
comparative signal so as to change the value of a control signal in such a
manner as to converge toward a target value corresponding to the reference
value in synchronism with a clock signal, the binary search unit
determining the value of the control signal at nth clock pulse of the
clock signal to be an intermediate value between the value of the control
signal at (n-1)th clock pulse of the clock signal and the value of the
control signal at (n-2)th clock pulse of the clock signal when the
comparator changes the comparative signal between a first state indicating
the output signal higher than the reference value and a second state
indicating the output signal lower than the reference value, the binary
search unit determining the value of the control signal at the nth clock
pulse of the clock signal in the present of the comparative signal
indicating one of the first state and the second state to be an
intermediate value between the value of the control signal at the (n-1)
clock pulse of the clock signal in the presence of the comparative signal
indicating the other of the first state and the second state and the
latest value of the control signal in the presence of the comparative
signal indicating the one of the first state and the second state; and a
shifting unit responsive to the control signal so as to change the output
signal.
The automatic regulating circuit may regulate a potential level to a
reference value.
BRIEF DESCRIPTION OF THE DRAWINGS
The features and advantages of the automatic regulating circuit according
to the present invention will be more clearly understood from the
following description taken in conjunction with the accompanying drawings
in which:
FIG. 1 is a circuit diagram showing the arrangement of the prior art
automatic regulating circuit;
FIG. 2 is a circuit diagram showing the arrangement of an automatic
regulating circuit according to the present invention;
FIG. 3 is a circuit diagram showing a binary search logic circuit
incorporated in the automatic regulating circuit;
FIG. 4 is a circuit diagram showing the arrangement of a switching unit
incorporated in the binary search logic circuit;
FIG. 5 is a graph showing an output voltage in terms of an clock pulse;
FIG. 6 is a circuit diagram showing the arrangement of a level shifter
incorporated in the automatic regulating circuit;
FIG. 7 is a circuit diagram showing another automatic regulating circuit
according to the present invention;
FIG. 8 is a circuit diagram showing the arrangement of a band-pass filter
incorporated in the automatic regulating circuit shown in FIG. 7; and
FIG. 9 is a diagram showing a function of a multiplier incorporated in the
automatic regulating circuit shown in FIG. 7.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
First Embodiment
Referring first to FIG. 2 of the drawings, an automatic regulating circuit
embodying the present invention comprises a reference voltage source 10
for generating a reference voltage Vref and a comparator having input
nodes connected to an output node Nout and the reference voltage source
10. The comparator 11 compares the output voltage signal Vout with the
reference voltage Vref, and generates a comparative signal CMP indicative
of a potential difference between the output voltage signal Vout and the
reference voltage Vref. The reference voltage Vref is variable, and may
range between 0.5 volt and 3.0 volts.
The automatic regulating circuit further comprises a binary search
controller 12 responsive to the comparative signal CMP so as to changing
an eight-bit digital control signal DCTL through a binary search sequence,
a digital-to-analog converter 13 for converting the eight-bit digital
control signal DCTL to an analog control signal ACTL and a level shifter
14 for shifting an input signal Vin. The level shifter 14 is incorporated
in an output circuit 15, and a series of resistor 15a, a bipolar
transistor 15b and a resistor 15c form the other part of the output
circuit 15. The regulated input signal V'in is supplied to the base node
of the bipolar transistor 15b, and the bipolar transistor 15b changes the
collector current Ic1 in response to the regulated input signal V'in. The
resistor 15c converts the collector current Ic1 to the output voltage
Vout.
In this instance, the binary search controller 12 and the digital-to-analog
converter 13 as a whole constitute a binary searching unit, and the level
shifter 14, the resistors 15a/15c and the bipolar transistor 15b form in
combination a shifting unit.
The binary search controller 12 gradually regulates the output voltage Vout
toward the reference voltage Vref, and the regulating sequence is as
follows. When the comparator 11 changes the comparative signal CMP at
every clock pulse, the binary search controller 12 regulates the target
output voltage Vout in such a manner as to have an intermediate value
between the value at the previous clock pulse and the value at the clock
pulse just before the previous clock pulse in so far as the sign is
changed. If the sign is not changed, the binary search controller 12 sets
the output voltage Vout to an intermediate value between the latest value
with the opposite sign and the value at the previous clock pulse. In the
first regulation, the binary search controller 12 regulates the new output
voltage to an intermediate value between the output voltage Vout at the
previous clock pulse and the maximum value Vmax in case of the output
voltage Vout greater than the reference voltage Vref and an intermediate
value between the output voltage Vout at the previous clock pulse and the
minimum value Vmin in case of the output voltage Vout less than the
reference voltage Vref.
The neutral value is set to an intermediate point between the maximum value
Vmax and the minimum value Vmin, and the output voltage Vout is assumed to
be changed from Vout(0) through Vout(1) to Vout(2). If the output voltage
Vout(0) is grater than the reference voltage Vref, i.e., Vout(0)>Vref, the
binary search logic controller 12 regulates the output voltage Vout(1)
through the digital-to-analog converter 13, the level shifter 14 and the
bipolar transistor 15b to an intermediate value between the output voltage
Vout(0) and the maximum value Vmax. Subsequently, if the output voltage
Vout(1) is still greater than the reference voltage Vref, i.e., Vout(1
)>Vref, the output voltage Vout(2) is regulated to an intermediate value
between the Vout (0) and Vout (1), because the output voltage Vout(2)
should be less than Vout(1). On the other hand, if the output voltage
Vout(1) is less than the reference voltage Vref, Vout(1)<Vref, the output
voltage Vout(2) is regulated to an intermediate value between Vout(1) and
Vmax.
In this way, the new output voltage Vout is sequentially changed through
the comparison between the present output voltage Vout and the reference
voltage Vref in synchronism with the clock signal CLK, and the output
voltage level Vout is finally matched with the reference voltage Vref at
the eighth clock pulse.
The binary search controller 12 includes a register 12a for supplying the
eight-bit digital control signal DCTL, a switch circuit 12b for
selectively changing the value of the eight-bit digital control signal
DCTL and a shift register 12c for selecting two bits to be changed from
the eight-bit digital control signal DCTL. The register 12a changes the
eight-bit digital control signal DCTL in synchronism with the clock signal
CLK as follows.
Assuming now that the register 12a stores the eight-bit digital control
signal DCTL of [10000000], the output voltage Vout(0) is initially
regulated to the mid point of the voltage regulating range.
If the output voltage Vout(0) is higher than the reference voltage Vref,
the switching circuit 12b adds "-1" to the second bit from the most
significant bit MSB of the eight-bit digital control signal DCTL at the
first clock pulse CLK(1) under the control of the shift register 12c, then
the eight-bit digital control signal DCTL is changed to [01000000]. On the
other hand, if the output voltage Vout(0) is lower than the reference
voltage, the switching circuit 12b adds "+1" to the second bit from the
most significant bit at the first clock pulse CLK(1) under the control of
the shift register 12c, and the eight-bit digital control signal DCTL is
changed to [11000000]. In the actual calculation, the switching circuit
12b supplies either "11" or "01" to the register 12a depending upon the
comparative signal CMP, and the shift register 12c sequentially designates
two bits of the eight-bit digital control signal DCTL from the most
significant bit MSB toward the least significant bit LSB.
The switching circuit 12b repeats the same calculation for the third bit
from the most significant bit MSB at the second clock pulse CLK(2) under
the control of the shift register 12c. In this way, the switching circuit
12b sequentially repeats the same calculation for (n+1) bit from the most
significant bit MSB at nth clock pulse under the control of the shift
register 12c, and the least significant bit LSB is treated with the
addition at seventh clock pulse CLK(7). When the addition is repeated
seven times, the output voltage Vout(7) reaches the closest value to the
reference voltage Vref.
FIG. 3 illustrates the circuit arrangement of the binary search controller
12. Eight D flip-flop circuits DFF0, DFF1, DFF2, DFF3, DFF4, DFF5, DFF6
and DFF7 and an OR gate OR1 form in combination the register 12a. The
clock signal CLK is supplied in parallel to the clock node C of the eight
D flip flop circuits DFF0 to DFF7, and the eight-bit digital control
signal DCTL is supplied from the output nodes Q of the D flip flop
circuits DFF0 to DFF7 to the output nodes T0 to T7. The reset signal RST
is supplied to the reset nodes R of the D flip flop circuits DFF0 to DFF6.
However, the reset signal RST is supplied through the OR gate OR1 to the D
flip flop circuit DFF7 as will be described hereinlater.
The switching circuit 12b includes eight switching units S10, S11, S12,
S13, S14, S15, S16 and S17 respectively associated with the D flip flop
circuits DFF0 to DFF7. A NAND gate NA1, two AND gates AD1 and AD2, an
inverter INV1 and an OR gate OR2 are incorporated in each of the switching
units S10 to S17 as shown in FIG. 4. The switching unit S10 to S17 has
four input nodes C, S1, S2 and I and an output node OUT. The comparative
signal CMP is supplied to the input nodes C of all the switching units S10
to S17, and the eight bits of the digital control signal DCTL are supplied
in parallel from the output nodes Q of the D flip flop circuits DFF0 to
DFF7 to the input nodes I of the switching units S10 to S17. As will be
described hereinbelow, the shift register 12c produces nine-bit output
signal, and the nine bits are selectively supplied to the input nodes
S1/S2 of the switching units S10 to S17. The output nodes OUT of the
switching units S10 to S16 are coupled in parallel to the input nodes D of
the D flip flop circuits DFF0 to DFF6. The output node OUT of the
remaining switching unit S17 is coupled to the OR gate OR1, and is ORed
with the reset signal RST. The output node of the OR gate OR1 is supplied
to the input node D of the D flip flop circuit DFF7.
The shift register 12c includes eight D flip flop circuits DFF10, DFF11,
DFF12, DFF13, DFF14, DFF15, DFF16, DFF17 and DFF18 and an OR gate OR3, and
the OR gate OR3 is coupled between the D flip flop circuits DFF18 and
DFF17. The clock signal CLK is supplied to the clock nodes C of the D flip
flop circuits DFF10 to DFF18, and the reset signal RST is supplied to the
reset nodes of the D flip flop circuits DFF10 to DFF16, the input node D
of the D flip flop circuit DFF18 and the OR gate OR3. The output node Q of
the D flip flop circuit DFF18 is coupled to the OR gate OR3, and is Red
with the reset signal RST. The output node of the OR gate OR3 is coupled
to the input node D of the D flip flop circuit DFF17. The output nodes Q
of the D flip flop circuits DFF17, DFF16, DFF15, DFF14, DFF13, DFF12 and
DFF11 are respectively coupled to the input nodes D of the adjacent D flip
flop circuits DFF16, DFF15, DFF14, DFF13, DFF12, DFF11 and DFF10.
Adjacent two D flip flop circuits are selected from the D flip flop
circuits DFF10 to DFF18, and the D flip flop circuits DFF10 to DFF18 form
eight groups.
The first group is constituted by the D flip flop circuits DFF10 and DFF11,
and the output nodes Q of the D flip flop circuits DFF11 and DFF10 are
coupled in parallel to the input nodes S1 and S2 of the switching circuit
S10.
The second group is constituted by the D flip flop circuits DFF11 and
DFF12, and the output nodes Q of the D flip flop circuits DFF12 and DFF11
are coupled in parallel to the input nodes S1 and S2 of the switching
circuit S11.
The third group is constituted by the D flip flop circuits DFF12 and DFF13,
and the output nodes Q of the D flip flop circuits DFF13 and DFF12 are
coupled in parallel to the input nodes S1 and S2 of the switching circuit
S12.
The fourth group is constituted by the D flip flop circuits DFF13 and
DFF14, and the output nodes Q of the D flip flop circuits DFF14 and DFF13
are coupled in parallel to the input nodes S1 and S2 of the switching
circuit S13.
The fifth group is constituted by the D flip flop circuits DFF14 and DFF15,
and the output nodes Q of the D flip flop circuits DFF15 and DFF14 are
coupled in parallel to the input nodes S1 and S2 of the switching circuit
S14.
The sixth group is constituted by the D flip flop circuits DFF15 and DFF16,
and the output nodes Q of the D flip flop circuits DFF16 and DFF15 are
coupled in parallel to the input nodes S1 and S2 of the switching circuit
S15.
The seventh group is constituted by the D flip flop circuits DFF16 and
DFF17, and the output nodes Q of the D flip flop circuits DFF17 and DFF16
are coupled in parallel to the input nodes S1 and S2 of the switching
circuit S16.
Finally, the eighth group is constituted by the D flip flop circuits DFF17
and DFF18, and the output nodes Q of the D flip flop circuits DFF18 and
DFF17 are coupled in parallel to the input nodes S1 and S2 of the
switching circuit S17.
When the automatic regulating circuit starts the potential regulation, the
reset signal RST is changed to logic "1" level. Then, the reset signal of
logic "1" level reaches the input nodes of the D flip flop circuits DFF18
and DFF17, the reset nodes R of the D flip flop circuits DFF16 to DFF10
and the input node D of the D flip flop circuit DFF7. The D flip flop
circuits DFF10 to DFF18 and DFF0 to DFF7 latches the logic levels at the
input nodes D in synchronism with the first clock pulse CLK. Then, the D
flip flop circuits DFF7 to DFF0 supply the eight-bit digital control
signal DCTL of [10000000] to the output nodes T7 to T0, and the D flip
flop circuits DFF18/DFF17 and the other D flip flop circuits DFF16 to
DFF10 produce the output bits of [11000000]. The reset signal RST is
recovered from logic "1" level to logic "0" level, and is maintained in
logic "0" level during the voltage regulation.
If the output voltage Vout is higher than the reference voltage Vref, the
comparative signal CMP is logic "1" level. On the other hand, the
comparative signal CMP of logic "0" level is indicative of the output
signal Vout lower than the reference voltage Vref.
The output voltage Vout is assumed to be lower than the reference voltage
Vref. As to the switching unit S17, the input nodes S1, S2 and I are at
logic "1" level, and the input node C is logic "0" level. In this
situation, the NAND gate NA1 produces logic "1", and logic "1" at the
input node S1 allows the AND gate AD1 to transfer logic "1" to the OR gate
OR2. For this reason, the OR gate OR2 yields logic "1" level at the output
node OUT of the switching unit S17 regardless of the output of the AND
gate AD2.
As to the switching unit S16, the input nodes S1, S2, I and C are in logic
"1", logic "0", logic "0" and logic "0". The NAND gate NA1 yields logic
"1" level, and the logic "1" level at the input node S1 allows the AND
gate AD1 to transfer logic "1" to the OR gate OR2. Then, the OR gate OR2
provides logic "1" level to the output node OUT of the switching unit S16
regardless of the output of the AND gate AD2.
On the other hand, if the output voltage Vout is higher than the reference
voltage, the comparative signal CMP is in logic "1", and the switching
units S17 and S16 produce logic "0" and logic "1".
As to each of the switching units S15 to S10, the input nodes S1, S2 and I
are in logic "0" level. Logic "0" at the input node I causes the AND gate
AD2 to produce logic "0", and logic "0" at the input node S1 causes the
AND gate AD1 to yield logic "0" regardless of the comparison signal CMP.
Thus, logic "0" is supplied to both inputs of the OR gate OR2, and the
switching units S15 to S10 produce logic "0" levels at the output nodes
OUT thereof.
The register 12a latches the output of the switching circuit 12b in
synchronism with the second clock signal CLK. The eight-bit digital
control signal DCTL is [11000000] in case of the output voltage Vout lower
than the reference voltage, and is an intermediate value between the
previous value [10000000] and the maximum value [11111111]. On the other
hand, the output voltage Vout higher than the reference voltage Vref
results in the eight-bit digital control signal DCTL of [01000000] which
is an intermediate value between the previous value [10000000] and the
minimum value [00000000]. The eight-bit digital control signal DCTL is
supplied to the output nodes T7 to T0.
The D flip flop circuits DFF18 and DFF17 transfer logic "1" levels to the D
flip flop circuits DFF17 and DFF16, and the D flip flop circuit DFF18
latches logic "0" level at the reset node of the D flip flop circuit DFF10
in synchronism with the second clock pulse. Thus, the shift register 12c
changes the output to [011000000] in synchronism with the second clock
pulse CLK. If the output voltage Vout is still lower than the reference
voltage Vref, the comparative signal CMP is still maintained in logic "0"
level.
As to the switching unit S17, logic "1" level and logic "0" level are
supplied to the input nodes S2 and I and the input nodes S1 and C. The
inverter INV1 causes the AND gate AD2 to produce logic "1" in the presence
of logic "1" level at the input node I, and the OR gate OR2 produces logic
"1" level regardless of the output of the AND gate AD1. As a result, the
switching unit S17 yields the output of logic "1" level at the output node
OUT thereof.
As to the switching unit S16, logic "1" level and logic "0" level are
supplied to the input nodes S1, S2 and I and the input node C. The NAND
gate NA1 produces logic "1", and logic "1" at the input node S1 allows the
AND gate AD1 to transfer logic "1" level to the OR gate OR2. The OR gate
OR2 transfers logic "1" to the output node OUT regardless of the output of
the AND gate AD2. As a result, the switching unit S16 produces logic "1"
at the output node OUT thereof.
As to the switching unit S15, logic "1" level and logic "0" level are
supplied to the input node S1 and the input nodes S2, I and C. The NAND
gate NA1 yields logic "1", and logic "1" at the input node S1 allows the
AND gate AD1 to transfer logic "1" to the OR gate OR2. The OR gate OR2
produces logic "1" regardless of the output of the AND gate AD2. Thus, the
switching unit S15 yields logic "1" level at the output node OUT thereof.
As to each of the switching units S14 to S10, logic "0" level is supplied
to all of the input nodes S1, S2, I and C. Although the NAND gate NA1
produces logic "1", logic "0" at the input node S1 causes the AND gate AD1
to change logic "1" of the NAND gate NA1 to logic "0". Logic "0" at the
input node I causes the AND gate AD2 to yield logic "0" level. As a
result, the OR gate OR2 supplies logic "0" level to the output node OUT of
each of the switching units S13 to S10.
Thus, the switching circuit 12b supplies the output of [11100000] to the
register 12a, and the register 12a latches the output of the switching
circuit 12b in synchronism with the third clock pulse CLK. The eight-bit
digital control signal DCTL has the value [11100000] between the previous
value [11000000] and the maximum value [11111111], because the comparative
signal CMP is assumed not to change the logic level.
The shift register 12c changes the output to [00110000] in synchronism with
the third clock pulse CLK. The comparative signal CMP is assumed to be
changed from logic "0" to logic "1" level. The switching circuit 12b
changes the outputs as follows.
As to the switching unit S17, logic "1" level and logic "0" level are
supplied to the input nodes I and C and the input nodes S1 and S2. The
inverter INV1 causes the AND gate AD2 to produce logic "1" level in the
presence of logic "1" at the input node I, and the OR gate transfers logic
"1" level to the output node OUT of the switching unit S17 regardless of
the output of the AND gate AD1. As a result, the switching unit S17 yields
logic "1" at the output nodes OUT.
As to the switching unit S16, logic "1" level and logic "0" level are
supplied to the input nodes S2, I and C and the input node S1. The
inverter INV1 causes the AND gate AD2 to produce logic "1" in the presence
of logic "1" at the input node I, and the OR gate OR2 transfers logic "1"
to the output node OUT of the switching unit S16 regardless of the output
of the AND gate AD1. Thus, the switching unit S16 yields logic "1" at the
output node OUT thereof.
As to the switching unit S15, logic "1" level are supplied to all of the
input nodes S1, S2, I and C. The NAND gate NA1 produces logic "0" level,
and the AND gate AD1 supplies logic "0" to the OR gate OR2. The inverter
INV1 causes the AND gate AD2 to produce logic "0", and the AND gate AD2
supplies logic "0" to the OR gate OR2. Logic "0" at both input nodes of
the OR gate OR2 results in logic "0" level at the output node OUT of the
switching unit S15. Thus, the switching unit S15 yields logic "0" level at
the output node OUT thereof.
As to the switching unit S14, logic "1" level and logic "0" level are
supplied to the input nodes S1 and C and the input nodes S2 and I. The
NAND gate NA1 produces logic "1", and the AND gate AD1 transfers logic "1"
to the OR gate OR2 in the presence of logic "1" at the input node S1. For
this reason, the OR gate OR2 transfers logic "1" to the output node OUT
regardless of the output of the AND gate AD2, and the switching unit S14
yields logic "1" at the output node OUT thereof.
As to the switching units S13 to S10, logic "1" level and logic "0" level
are supplied to the input node C and the input nodes S1, S2 and I. Logic
"0" at the input node S1 and logic "0" at the input node I cause the AND
gates AD1 and AD2 to produce logic "0", and the OR gate OR2 transfers
logic "0" to the output node OUT. Thus, the switching units S13 to S10
yield logic "0" at the output nodes OUT thereof.
Thus, the switching circuit 12b supplies the output of [11010000] to the
register 12a, and the register 12a latches the output of [11101000] in
synchronism with the fourth clock signal CLK. The eight-bit digital
control signal DCTL has the value [11010000] between the previous two
values, i.e., [11000000] and [11100000], because the comparative signal
CMP changes the logic level from "0" to "1".
The shift register 12c changes the output to [000110000] in synchronism
with the fourth clock pulse CLK, and the comparative signal CMP is assumed
to change the logic level from "1" to "0". The output of the switching
circuit 12b becomes as follows.
As to each of the switching units S17 and S16, logic "1" and logic "0" are
supplied to the input node I and the input nodes S1, S2 and C. The
inverter INV1 causes the AND gate AD2 to produce logic "1" in the presence
of logic "1" at the input node I, and the OR gate OR2 transfers logic "1"
to the output node OUT regardless of the output of the AND gate AD1. For
this reason, the switching units S17 and S16 yield logic "1" at the output
nodes OUT thereof.
As to the switching unit S15, logic "1" and logic "0" are supplied to the
input node S2 and the input nodes S1, I and C. Logic "0" at the input node
S1 causes the AND gate AD1 to produce logic "0" regardless of the output
of the NAND gate NA1, and logic "0" at the input node I also causes the
AND gate AD2 to produce logic "0". Logic "0" is supplied to both inputs of
the OR gate OR2, and the OR gate OR2 supplies logic "0" to the output node
OUT. Thus, the switching unit S15 yields logic "0" at the output node OUT
thereof.
As to the switching unit S14, logic "1" and logic "0" are supplied to the
input node S1, S2 and I and the input node C. The NAND gate NA1 produces
logic "1" level, and logic "1" level at the input node S1 allows the AND
gate AD1 to transfer logic "1" level to the OR gate OR2. The OR gate OR2
supplies logic "1" level to the output node OUT regardless of the output
of the AND gate AD2, and the switching unit S14 yields logic "1" level at
the output node OUT thereof.
As to the switching unit S13, logic "1" and logic "0"are supplied to the
input node S1 and the input nodes S2, I and C. The NAND gate NA1 produces
logic "1", and logic "1" at the input node S1 allows the AND gate AD1 to
transfer logic "1" to the OR gate OR2. As a result, the OR gate OR2
supplies logic "1" to the output node OUT regardless of the output of the
AND gate AD2. Thus, the switching unit S13 yields logic "1" level at the
output node OUT thereof.
As to the switching units S12 to S10, logic "0" is supplied to all of the
input nodes S1, S2, I and C. Logic "0" level at the input nodes S1 and I
causes the AND gates AD1 and AD2 to produce logic "0" level, and the OR
gate OR2 supplies logic "0" to the output node OUT. Thus, the switching
units S12 to S10 yield logic "0" at the output nodes OUT thereof.
The switching circuit 12b supplies the output of [1101000] to the register
12a, and the register 12a latches the output of [11011000] in synchronism
with the fifth clock pulse CLK. The eight-bit digital control signal DCTL
has the value [110111000] between the latest value [11100000] in the
presence of the comparative signal CMP of logic "0" level and the previous
value of [11010000].
In this way, the shift register 12c transfers the two logic "1" bits from
the eighth group to the first group in synchronism with the clock signal
CLK, and the switching units S10 to S17 change the logic levels at the
respective output nodes OUT through the logical operation on the previous
value of the digital control signal DCTL, the two bits S1 and S2 supplied
from the shift register 12c and the comparative signal CMP. The register
12a latches the logic levels at the output nodes OUT in synchronism with
the clock signal CLK, and the eight bit digital control signal DCTL is
changed for the binary search.
Turning to FIG. 6 of the drawings, the level shifter 14 includes a
capacitor CP1 and a series of resistor 14a, a bipolar transistor 14b and a
resistor 14c coupled between a positive power voltage line and a ground
voltage line, and the capacitor CP1 is coupled between the input node for
the input voltage signal Vin and the collector node of the bipolar
transistor 14b. The regulated input voltage signal V'in appears at the
collector node of the bipolar transistor 14b. The analog control signal
ACTL is supplied to the base node of the bipolar transistor 14b.
If the binary search controller 12 changes the eight-bit digital control
signal DCTL and, accordingly, the digital-to-analog converter 13 changes
the analog control signal ACTL, the bipolar transistor 14b changes the
collector current Ic2, and the resistor 14a changes the potential drop
depending upon the amount of the collector current Ic2. As a result, the
regulated input signal V'in varies the potential level as given by
equation 1.
V'in=Vcc-R1.times.Ic2 Equation 1
where Vcc is the potential level on the positive power voltage line and R1
is the resistance of the resistor 14a. Thus, the level shifter 14 changes
the potential level of the input voltage signal Vin in response to the
analog control signal ACTL.
With the eight-bit digital control signal DCTL, the level shifter 14
regulates the output voltage Vout in cooperation with the bipolar
transistor 15b as follows. First we assume that the reference voltage
Vref, the initial output voltage Vout(0), the maximum voltage Vmax and the
minimum voltage Vmin are 2.5 volts, 1.5 volts, 3.0 volts and 0 volt,
respectively, and FIG. 5 illustrates the voltage regulation on the output
voltage Vout.
After the reset signal RST is supplied to the shift register 12c and the
register 12a, the eight-bit digital control signal DCTL is changed to
[10000000] in synchronism with the first clock pulse CLK(0), and the
digital-to-analog converter 13 converts the eight-bit digital control
signal DCTL of [10000000] to the corresponding analog control signal ACTL.
The level shifter 14 changes the input voltage signal from Vin to V'in,
and causes the bipolar transistor 15b to change the collector current Ic.
The collector current Ic is converted to the output voltage Vout(0)
corresponding to the eight-bit digital control signal DCTL of [10000000],
and is 1.5 volt.
The output voltage Vout(0) is lower than the reference voltage Vref, and
the switching circuit 12b changes the output thereof to [11000000]. The
register 12a latches the output of the switching circuit 12b in
synchronism with the second clock signal CLK(1), and the level shifter 14
and the bipolar transistor 15b changes the collector current Ic to the
value corresponding to the eight-bit digital control signal DCTL. As a
result, the output voltage Vout(1) is regulated to (Vout(0)+Vmax)/2=2.25
volts.
The output voltage Vout(1) is still lower than the reference voltage Vref,
and the switching circuit 12b changes the output thereof to [11100000].
The register 12a latches the output of the switching circuit 12b in
synchronism with the third clock signal CLK(2), and the level shifter 14
and the bipolar transistor 15b changes the collector current Ic to the
value corresponding to the eight-bit digital control signal DCTL. As a
result, the output voltage Vout(2) is regulated to (Vout(1)+Vmax)/2=2.63
volts.
The output voltage Vout(2) is higher than the reference voltage Vref, and
the switching circuit 12b changes the output thereof to [11010000]. The
register 12a latches the output of the switching circuit 12b in
synchronism with the fourth clock signal CLK(3), and the level shifter 14
and the bipolar transistor 15b changes the collector current Ic to the
value corresponding to the eight-bit digital control signal DCTL. As a
result, the output voltage Vout(3) is regulated to
(Vout(2)+Vout(1))/2=2.44 volts.
The output voltage Vout(3) is lower than the reference voltage Vref, and
the switching circuit 12b changes the output thereof to [11011000]. The
register 12a latches the output of the switching circuit 12b in
synchronism with the fifth clock signal CLK(4), and the level shifter 14
and the bipolar transistor 15b change the collector current Ic to the
value corresponding to the eight-bit digital control signal DCTL. As a
result, the output voltage Vout(4) is regulated to
(Vout(3)+Vout(2))/2=2.53 volts.
The output voltage Vout(4) is higher than the reference voltage Vref, and
the switching circuit 12b changes the output thereof to [11010100]. The
register 12a latches the output of the switching circuit 12b in
synchronism with the sixth clock signal CLK(5), and the level shifter 14
and the bipolar transistor 15b change the collector current Ic to the
value corresponding to the eight-bit digital control signal DCTL. As a
result, the output voltage Vout(5) is regulated to
(Vout(4)+Vout(3))/2=2.49 volts in response to the sixth clock pulse
CLK(5).
The output voltage Vout(5) is lower than the reference voltage Vref, and
the switching circuit 12b changes the output thereof to [11010110]. The
register 12a latches the output of the switching circuit 12b in
synchronism with the seventh clock signal CLK(6), and the level shifter 14
and the bipolar transistor 15b change the collector current Ic to the
value corresponding to the eight-bit digital control signal DCTL. As a
result, the output voltage Vout (6) is regulated to (Vout
(5)+Vout(4))/2=2.51 volts in response to the seventh clock pulse CLK (6).
The output voltage Vout(6) is higher than the reference voltage Vref, and
the switching circuit 12b changes the output thereof to [11010101]. The
register 12a latches the output of the switching circuit 12b in
synchronism with the eighth clock signal CLK(7), and the level shifter 14
and the bipolar transistor 15b change the collector current Ic to the
value corresponding to the eight-bit digital control signal DCTL. As a
result, the output voltage Vout(7) is regulated to (Vout(6)+Vout(5))/2
=2.50 volt in response the eighth clock pulse CLK(7).
The switching circuit 12b shifts two bits from the most significant bit MSB
to the least significant bit LSB in synchronism with the clock signal CLK,
and the two bits are changed to "11" or "01" depending upon the
comparative signal CMP. In the above described example, the two bits are
changed as follows.
______________________________________
clock pulse
DCTL
______________________________________
first 10000000
second 11000000
third 11100000
fourth 11010000
fifth 11011000
sixth 11010100
seventh 11010110
eighth 11010101
______________________________________
As will be understood from the foregoing description, the binary search
controller 12 changes the value of the eight-bit control signal across a
target value corresponding to the reference voltage Vref in synchronism
with the clock signal CLK, and the value of the eight-bit control signal
converges at the target value. Accordingly, the level-shifter 14 and the
bipolar transistor 15b changes the output voltage Vout in response to the
analog control signal formed from the eight-bit digital control signal,
and the output voltage Vout also converges at the reference voltage Vref.
The automatic regulating circuit according to the present invention
completes the voltage regulation at eighth clock pulse at all times, and
regulates the output voltage Vout to the reference voltage Vref faster
than the prior art automatic regulating circuit. Even if another signal
processing follows, the designer can share long time period to the signal
processing, and the circuit design becomes easier.
Second Embodiment
Turning to FIG. 7 of the drawings, another automatic regulating circuit
embodying the present invention is used for a frequency regulation. The
automatic regulating circuit comprises a comparator 21, a reference
voltage source 22, a binary search controller 23, a phase shifter 24, a
band-pass filter 25, a multiplier 26 and a capacitor 27. The comparator 21
and the reference voltage source 22 are similar to those of the first
embodiment.
The phase shifter 24 shifts the phase of an input signal Sin by 90 degrees,
and supplies an phase-shifted signal S'in to the multiplier 26. The input
signal Sin is transferred from the phase shifter 24 to the band-pass
filter 25, and the band-pass filter 25 produces an output signal Sout
under the control of the binary search controller 23. The multiplier 26
multiplies the output signal Sour by the phase-shifted signal S'in, and
the multiplier 26 supplies a product signal PDT to the capacitor 27, and
the capacitor 27 smoothen the product signal PDT. The product signal PDT
is supplied through the capacitor 27 to the comparator 21. The comparator
compares the product signal PDT with the reference voltage signal Vref,
and supplies a comparative signal CMP indicative of a potential difference
between the product signal PDT and the reference voltage signal Vref. The
potential difference between the product signal PDT and the reference
voltage signal Vref represents an offset of the center frequency f0 in the
band-pass filter 25.
The binary search controller 23 changes the value of a digital control
signal across a target value corresponding to the reference voltage Vref,
and the digital control signal converges at the target as similar to the
first embodiment.
After conversion into an analog control signal ACTL, the binary search
controller 23 supplies the analog control signal ACTL to the control node
of the band-pass filter 25, and the band-pass filter 25 regulates the
center frequency thereof f0.
If the frequency of the input signal Sin is equal to the center frequency
f0, the phase of the output signal Sout is zero degree. However, if the
frequency of the input signal Sin is offset from the center frequency f0,
the phase of the output signal Sour is changed depending upon the
magnitude of the offset.
The band-pass filter 25 is arranged in such a manner as to control the
center frequency f0 with the analog control signal ACTL. FIG. 8
illustrates the arrangement of the band-pass filter 25. Two operational
amplifiers 25a and 25b and three capacitors 25c, 25d and 25e form in
combination an active filter for the band-pass filter 25, and the
transconductance gm of the operational amplifiers 25a and 25b is
controlled by the analog control signal ACTL.
The transfer function of the active filter 25 is given by equation 2.
x=S1/{S2(S1+S3)+S1+1} equation 2
where "1" is the input, x is the output and S1, S2 and S3 are transfer
functions of the capacitors 25c, 25e and 25d.
FIG. 9 shows the function of the multiplier 26. If the output signal S' in
is exactly shifted by 90 degrees, the multiplier 26 produces the product
signal PDT1 corresponding to the overlapped portion OV1 between the input
signal Sin and the phase-shifted signal S' in.
However, if the output signal S'in is shifted by (90-a) degrees, the
multiplier 26 produces the product signal PDT2 wider than the standard
product signal PDT1. On the other hand, if the output signal S'in is
shifted by (90+a) degrees, the multiplier 26 produces the product signal
PDT3 narrower than the standard product signal PDT1. For this reason,
after the smoothening by the capacitor 27, the potential level of the
product signal PDT is indicative of the phase difference, and the
comparator 21 compares the potential level of the product signal PDT with
the reference voltage Vref.
The reference voltage Vref is calculated through the integration between
the capacitance of the capacitor 27 and the standard product signal PDT at
the cycle frequency of the input signal matched with the center frequency
of the band-pass filter 25.
The automatic regulating circuit thus arranged quickly regulates the output
signal Sour to the standard input signal, and the phase shifter 24, the
band-pass filter 25, the multiplier 26 and the capacitor 27 form in
combination a shifting unit.
As will be appreciated from the foregoing description, the binary search
controller quickly regulates the output signal to a reference value in
cooperation with the shifting unit.
Although particular embodiments of the present invention have been shown
and described, it will be obvious to those skilled in the art that various
changes and modifications may be made without departing from the spirit
and scope of the present invention.
For example, the binary search controller may supply a digital control
signal more than eight bits to the digital-to-analog converter 13. The
bits of the digital control signal is dependent on the resolution for the
potential control range, and is optimized on the balance between the
resolution and the response time.
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