Back to EveryPatent.com
| United States Patent |
5,251,120
|
|
Smith
|
October 5, 1993
|
Harmonic noise isolation and power factor correction network
Abstract
A network for connection between an AC power line and a DC power supply to
isolate harmonic currents generated by the DC power supply from the AC
power supply, the network employing at least one "resonator", which is
connected across the input of a DC power supply, and at least one
"reflector", which is connected to couple the input of the DC power supply
to an AC power line. Each "resonator," includes the series combination of
an inductor and a capacitor. At least some of the "reflectors" include the
parallel combination of an inductor and a capacitor.
| Inventors:
|
Smith; Steve (5100 Channel Ave., Richmond, CA 94804)
|
| Appl. No.:
|
817927 |
| Filed:
|
January 2, 1992 |
| Current U.S. Class: |
363/44; 363/126 |
| Intern'l Class: |
H02M 001/12 |
| Field of Search: |
363/39,44-48,126
333/175,176,167,81
|
References Cited
U.S. Patent Documents
| 3133259 | May., 1964 | Van Dine | 363/44.
|
| 4672522 | Jan., 1987 | Lesea | 363/48.
|
| 5113335 | May., 1992 | Smith | 363/44.
|
| 5148359 | Sep., 1992 | Nguyen | 363/48.
|
| Foreign Patent Documents |
| 258576 | Mar., 1988 | EP.
| |
| 1927415 | Jan., 1970 | DE.
| |
| 3012747 | Oct., 1981 | DE | 363/44.
|
| 157261 | Dec., 1981 | JP | 363/44.
|
Primary Examiner: Beha, Jr.; William H.
Attorney, Agent or Firm: Schatzel; Thomas E.
Parent Case Text
CROSS REFERENCE TO RELATED APPLICATIONS
This patent application is a continuation-in-part of the U.S. patent
application Ser. No. 06/888,137, which was filed on Jul. 23, 1986, now
U.S. Pat. No. 5,113,535.
Claims
What is claimed is:
1. A harmonic noise isolation and power factor correction network that has
an input to output impedance magnitude, in ohms, that is at least ten
percent of an input voltage, in volts, divided by a resulting current
through the network, in amperes, at a predetermined power line frequency,
the network comprising:
a pair of first and second power input terminals for receiving a single
phase alternating current (AC) power input of said predefined power line
frequency;
a pair of first and second power output terminals for driving a
capacitor-input rectifier combination that generates odd harmonics of said
predefined power line frequency and that has a constant conduction angle,
said second output terminal being in common with said second input
terminal;
a first two-terminal parallel resonant circuit including a first parallel
inductor in parallel with a first parallel capacitor, and having a first
resonant frequency, the first parallel resonant circuit being connected in
series between said first power input terminal and said first power output
terminal, the first two-terminal parallel resonant circuit having a
resonant frequency approximately equal to five times said predefined power
line frequency; and
one and only one two-terminal series resonant circuit including a first
series inductor connected in series with a first series capacitor, the
first series resonant circuit being connected in shunt with said first and
second output terminals, the series resonant circuit having a resonant
frequency approximately equal to an odd harmonic plus one half times said
predefined power line frequency.
2. The network of claim 1, further comprising:
a second two-terminal parallel resonant circuit including a second parallel
inductor in parallel with a second parallel capacitor and a resistor in
series, the second parallel resonant circuit being connected in series
with the first parallel resonant circuit and in series between said first
power input terminal and said first power output terminal, the second
two-terminal parallel resonant circuit having a resonant frequency
approximately equal to seven times said predetermined power line
frequency.
3. The network of claim 2, further comprising
a third two-terminal parallel resonant circuit including a third parallel
inductor and a third parallel capacitor, the third parallel resonant
circuit being connected in series with both the first and second parallel
resonant circuits and all the parallel resonant circuits connected in
series with one another between said first power input terminal and said
first power output terminal, the third two-terminal parallel resonant
circuit having a resonant frequency approximately equal to three times
said predefined power line frequency.
4. The network of claim 1, further comprising:
an AC-to-direct-current (DC) power conversion means with a power load and
that is coupled to said first and second power output terminals and that
does not vary its rectification conduction angles such that a spurious
noise with an unvarying harmonic content is presented to said first and
second power output terminals during operation wherein such spurious noise
is thereby substantially blocked from backing through to said first and
second power input terminals by the parallel and series resonant circuits
and their harmonic combination topology.
5. The network of claim 4, wherein:
the AC-to-DC power conversion means further includes a full-wave rectifier
that generates said spurious noise at predictable odd harmonics of said
predefined power line frequency.
6. The network of claim 1, wherein:
the two-terminal series resonant circuit has a resonant frequency that is
substantially five and one-half times said predefined power line
frequency.
7. The network of claim 1, wherein:
the two-terminal series resonant circuit has a circuit-Q that is within a
range of 0.5 to 3.0.
8. The network of claim 3, wherein:
the first through third two-terminal parallel resonant circuits present an
impedance with a magnitude, in ohms, that is at least ten percent of a
voltage applied across said first and second power input terminals, in
volts, divided by a resulting current through the first two-terminal
parallel resonant circuit, in amperes, at said predetermined power line
frequency.
9. The network of claim 1, further comprising:
a damping circuit including a damping resistor connected in series with a
damping capacitor, the damping circuit being connected in parallel with
the series resonant circuit and with said first and second output
terminals.
10. The network of claim 1, wherein:
the two-terminal series resonant circuit has an impedance substantially
within a range of 240 ohms to 330 ohms at said resonant frequency.
11. The network of claim 3, wherein:
the two-terminal series resonant circuit has an impedance substantially
within a range of 240 ohms to 330 ohms at said resonant frequency; and
said resistor included in the second two-terminal parallel resonant circuit
is substantially equal in resistance to said impedance of two-terminal
series resonant circuit.
12. A harmonic noise isolation and power factor correction network,
comprising:
a pair of first and second power input terminals for receiving a single
phase alternating current (AC) power input of a predefined power line
frequency;
a pair of first and second power output terminals, said second output
terminal being in common with said second input terminal;
a first two-terminal parallel resonant circuit including a first parallel
inductor in parallel with a first parallel capacitor, and having a first
resonant frequency, the first parallel resonant circuit being connected in
series between said first power input terminal and said first power output
terminal;
a second two-terminal parallel resonant circuit including a second parallel
inductor in parallel with a second parallel capacitor and a resistor in
series, and having a second resonant frequency, the second parallel
resonant circuit being connected in series with the first parallel
resonant circuit;
a third two-terminal parallel resonant circuit including a third parallel
inductor and a third parallel capacitor and having a third resonant
frequency, the third parallel resonant circuit being connected in series
with both the first and second parallel resonant circuits and all the
parallel resonant circuits being connected in series with one another
between said first power input terminal and said first power output
terminal;
a two-terminal series resonant circuit including a first series inductor
connected in series with a first series capacitor, the first series
resonant circuit being connected in shunt with said first and second
output terminals and having a resonant frequency approximately five and
one-half times said predetermined power line frequency; and
a damping circuit including a damping resistor connected in series with a
damping capacitor, the damping circuit being connected in parallel with
the series resonant circuit and with said first and second output
terminals.
13. The network of claim 12, wherein
said first resonant frequency is approximately five times said
predetermined power line frequency;
said second resonant frequency is approximately seven times said predefined
power line frequency; and
said third resonant frequency is approximately three times said predefined
power line frequency.
Description
BACKGROUND OF THE INVENTION
1. Field of the Invention
The present invention relates to the power factor which loads present to AC
power lines generally and more specifically to the reduction of the
harmonic currents generated on an AC power line by a DC power supply.
2. Description of the Prior Art
The power factor that a load presents to an AC power line has long been of
concern. At one time, the primary concern was the inductive component of
some loads. Consider, for example, the section taken from the text
entitled American Electricians' Handbook (8th ed. 1961) which was edited
by Terrell Croft, revised by Clifford C. Carr, and published by McGraw
Hill Inc.
"143. Correction of Low Power Factor. In industrial plants, excessively
low power factor is usually due to underloaded induction motors because
the power factor of motors is much less at partial loads than at full
load. Where motors are underloaded new motors of small capacity should be
substituted. Power factor can be corrected (1) by installing synchronous
motors (2) by connecting static capacitors across the line." (end of
section)
Of late, the "power factor" presented by DC power supplies has become a
concern. Typically, DC power supplies employ a bridge rectifier, a filter
capacitor, and, sometimes, a filter choke. The input of the rectifier is
coupled (by a fuse, switch, etc.) across an AC power line. The output of
the rectifier is either coupled by the choke across the capacitor (choke
input filter) or, absent the choke, directly connected across the
capacitor (capacitor-input filter) to develop a DC (output) potential
across the capacitor.
With the choke (input filter), DC power supplies draw from the AC power
line a current the waveform of which approximates a square wave (when the
inductance of the choke is much greater than what is commonly referred to
as the "critical" inductance). Absent the choke, the waveform more
approximates a series of pulses each of which is synchronized with a
corresponding peak of the AC power-line potential. In either case, the
current drawn from the AC power line includes harmonic components
(currents), one for each of the odd harmonics of the AC power-line
frequency.
The level of the harmonic currents generated on both a three-phase and a
single-phase AC power power line by both a choke-input and a
capacitor-input, full-wave, DC power supply were calculated. The DC power
supply was directly connected to the AC power line; and, a load resistor
was directly connected across the DC power supply filter capacitor. (Small
resistors were included in series with various components to facilitate
the calculations.) The calculations were performed by a computer program
entitled Micro-Cap II by Spectrum Software. An rms AC power line potential
of 120 volts was used.
______________________________________
Harmonic currents generated on an three-phase AC power
line by a choke-input, full-wave, DC power supply
level of the harmonic currents
relative the fundamental
______________________________________
1st 100.0%
2nd 0.0%
3rd 0.2%
4th 0.0%
5th 19.8%
6th 0.0%
7th 14.4%
8th 0.0%
9th 0.2%
10th 0.0%
11th 8.9%
12th 0.0%
13th 7.8%
14th 0.0%
15th 0.2%
16th 0.0%
17th 5.7%
18th 0.0%
19th 5.3%
20th 0.0%
21st 0.3%
22nd 0.0%
23rd 4.2%
24th 0.0%
25th 4.1%
26th 0.0%
27th 0.3%
28th 0.0%
29th 3.3%
______________________________________
Total
Harmonic
Load Power Frequency Output Level
______________________________________
2000 Watt
2000 W 60 Hz 158 V DC
30.0%
______________________________________
______________________________________
Harmonic currents generated on an three-phase AC power
line by a capacitor-input, full-wave, DC power supply
level of the harmonic currents
relative the fundamental
______________________________________
1st 100.0%
2nd 0.0%
3rd 0.1%
4th 0.0%
5th 62.7%
6th 0.0%
7th 36.0%
8th 0.0%
9th 0.0%
10th 0.0%
11th 3.7%
12th 0.0%
13th 8.6%
14th 0.0%
15th 0.1%
16th 0.0%
17th 2.9%
18th 0.0%
19th 1.9%
20th 0.0%
21st 0.0%
22nd 0.0%
23rd 2.8%
24th 0.0%
25th 0.7%
26th 0.0%
27th 0.0%
28th 0.0%
29th 2.0%
______________________________________
Total
Harmonic
Load Power Frequency Output Level
______________________________________
2000 Watt
2000 W 60 Hz 153 V DC
73.1%
______________________________________
______________________________________
Harmonic currents generated on a single-phase AC power
line by a capacitor-input, full-wave, DC power supply
level of the harmonic currents
relative the fundamental
______________________________________
1st 100.0%
2nd 0.0%
3rd 94.9%
4th 0.0%
5th 85.2%
6th 0.0%
7th 72.1%
8th 0.0%
9th 56.9%
10th 0.0%
11th 41.3%
12th 0.0%
13th 26.8%
14th 0.0%
15th 15.2%
16th 0.0%
17th 8.7%
18th 0.0%
19th 8.7%
20th 0.0%
21st 10.1%
22nd 0.0%
23rd 10.0%
24th 0.0%
25th 8.3%
26th 0.0%
27th 5.7%
28th 0.0%
29th 3.4%
30th 0.0%
31st 3.0%
32nd 0.0%
33rd 3.7%
34th 0.0%
35th 4.1%
36th 0.0%
37th 3.8%
38th 0.0%
39th 2.8%
40th 0.0%
41st 1.7%
42nd 0.0%
43rd 1.3%
44th 0.0%
45th 1.7%
46th 0.0%
47th 2.0%
48th 0.0%
49th 2.0%
50th 0.0%
______________________________________
Power Factor
______________________________________
0.42
______________________________________
Total
Harmonic
Load Power Frequency Output Level
______________________________________
200 Ohms 131 W 60 Hz 162 V DC
167%
______________________________________
It is important to note that a DC power supply employing a full wave
rectifier (such as a bridge rectifier) (with properly balanced
transformer, if employed, and rectifier diodes) generates harmonic
currents only at the ODD harmonics of the AC power line frequency. (See,
for example, the fifth, 1968, edition of Howard W. Sams & Co., Inc. (ITT)
Reference Data For Radio Engineers section 42-8 "Odd or Even Harmonics,"
where it is stated that:
"(a) condition that causes a function f(x) of period 2(pi) to have only
odd harmonics in its Fourier expansion is f(x)=-f(x+pi)."
(Even if the transformer, if employed, and the rectifier diodes are not
properly balanced, the level of the currents at even harmonics of the AC
power line frequency will, normally, be negligible.)
DC power supplies do not conform to all of the old power factor
conventions. (For example, it makes little sense to define the power
factor a DC power supply presents to an AC power line as the cosine of the
phase angle between the voltage developed across the input of the DC power
supply and the current flowing into it.) However, they (DC power supplies)
do present many of the same problems. DC power supplies, like other loads
having a relatively low power factor, draw from the AC power line a
current the rms level of which is disproportionately high in relation to
the current that should be drawn for the power consumed. (In other words,
they do conform to the definition which states that the power factor of a
load (in this case, a DC power supply) is given by the ratio of the actual
power consumed (in this case by a load connected to the output of the DC
power supply) (as indicated by a wattmeter) to the apparent power (as
indicated by the combination of a (true rms, iron-vane or
thermocouple-type) ammeter and a voltmeter) (connected to the input of the
DC power supply).
A relatively high AC power-line rms current is of concern in that the AC
power-generating facilities and AC power-transmission facilities (lines
and transformers) must be sized to accommodate the current. Further,
generation and transmission losses are primarily resistive losses which,
therefore, increase as the square of the level of the rms AC power-line
current. It is important to note that even relatively small loads (DC
power supplies) may be of concern. Although a small personal computer, for
example, may not draw the level of the current drawn by a large smoke
stack scrubber, if the DC power supply of the computer has a relatively
low power factor, the current drawn by the DC power supply may be of such
a level as to limit what may also be plugged into a single AC power-line
wall outlet.
In addition, DC power supplies present many special problems, particularly
for the military. As the number of airborne and shipborne systems
employing DC power supplies has increased, so has the level of harmonic
currents generated on the various AC power lines. With the increased
levels of harmonic currents has come an increase in the above mentioned
generation and transmission problems. In addition, and of potentially much
more serious consequence, the high levels of harmonic currents are causing
problems of undesired system interaction. As a consequence, standards have
been promulgated including those in the Department of Defense document
which is identified as DOD-STD-1399(NAVY) SECTION 300 1 AUG. 1978 and
which is entitled MILITARY STANDARD INTERFACE STANDARD FOR SHIPBOARD
SYSTEMS SECTION 300 ELECTRIC POWER, ALTERNATINC CURRENT. Of particular
relevance is the following section.
"6.2.7 Harmonic current. The operation of equipment shall be designed to
have minimum harmonic distortion effect on the electrical system. The
operation of such equipment with the following specified ratings shall not
cause harmonic line currents to be generated that are greater than 3
percent of the unit's full load fundamental current between the 2nd and
32nd harmonic. . . ."
(For a power-source frequency of 60 Hz, a 1 kVA or more unit rating is
specified.)
"Additionally, currents with frequencies from the 32nd harmonic through 20
kilohertz (kHz) shall not exceed 100/n percent . . ."
In Table I. (on page 5) the total harmonic distortion is limited to 5
percent; and, in section 6.2.2 the power factor is limited to the range of
0.8 lagging to 0.95 leading. Further, in Table I. (on page 5) the worst
case frequency excursion from nominal frequency is listed as 51/2 percent.
Heretofore, great difficulty has been had in meeting the above-mentioned
standard.
It has been suggested that a filter be used to "trap and shunt undesirable
harmonics." To illustrate the the problems associated with the use of a
filter to isolate from an AC power line, harmonic currents a DC power
supply would, otherwise, generate on the line, performance characteristics
were calculated for a circuit in which the above-mentioned
(capacitor-input-type) DC power supply was coupled to the line by means of
a filter designed to match a zero ohm source (driving) impedance to a 144
ohm load impedance. Specifically, an 8-pole, Butterworth, low pass filter
was designed. (First, for low, pass band attenuation, 60 Hz was set equal
to 0.7 omega, making omega equaled to 86 Hz. Next, it was noted that when
the above-mentioned (capacitor-input-type) DC power supply was directly
connected to the AC power line, the third harmonic level was approximately
94%. Also, it was noted that the above-mentioned military specification
required that the third harmonic level not exceed 3%. Thus, an 8-pole
filter (n equal 8) was chosen to provide an approximate 30:1 voltage
reduction (approximately 50 dB) at 180 Hz (2.1 omega). Also chosen was a d
of 0.02.
As a consequence for the 8-pole, Butterworth, low pass filter:
______________________________________
L(1) = 1.398 C(2) = 1.963
L(3) = 1.648 C(4) = 1.602
L(5) = 1.243 C(6) = 0.9613
L(7) = 0.5829 C(8) = 0.1982.
______________________________________
(Where L(1) is connected in series with the AC power line; and, C(8) is
connected across the input of the DC power supply.) These component values
were scaling for omega equal to two pi times 86 Hz. and Z(0) equal to 144
ohms. (L' equals 144 divided by the quantity of two pi times 86 Hz.; and,
C' equals one divided by the quantity 144 times two pi times 86 Hz.) (See,
for example, pages 7, 8, and 136 of the first edition (1963) of the book
by Philip R. Geffe which is entitled Simplified Modern Filter Design.) As
a consequence:
______________________________________
L(1) = 0.3726 H C(2) = 25.23 mfd
L(3) = 0.4392 H C(4) = 20.59 mfd
L(5) = 0.3312 H C(6) = 12.35 mfd
L(7) = 0.1553 H C(8) = 2.547 mfd.
______________________________________
______________________________________
Harmonic currents generated on an AC power line by a DC
power supply coupled to the line by the 8-pole, Butterworth,
low pass filter
level of the harmonic currents
relative the fundamental
______________________________________
1st 100.00%
2nd 0.22%
3rd 0.08%
4th 0.08%
5th 0.07%
6th 0.06%
7th 0.06%
8th 0.06%
9th 0.05%
______________________________________
Total
Harmonic
Load Power Frequency Output Level
______________________________________
200 Ohms 50 W 60 Hz 100 V DC
0.4%
______________________________________
It is important to note the relatively low potential (100 volts) which was
developed across the load, as compared to the 162 volt DC potential which
was developed by the DC power supply across the 200 ohm (131 watt) load
without the filter. In addition, the circuit exhibited a number of other,
undesirable, characteristics. Noted was a 15 ms delay, a 32 ms overshoot,
a resonant boost, a current lag, and an impulse in the output following
the start impulse. Further, the phase angle of the fundamental would
suggest a power factor of 0.66. Finally, it is important to note the size
of the components.
The use of series-connected, parallel-resonant, inductor-capacitor-type "LC
filters" is shown in three prior-art patents. The German patent DE
3012-747 of Wilhelm Kleische shows (in the sole figure) what is referred
to (in the Abstract) as an "LC filter circuit". The "LC filter circuit"
includes the parallel combination of an inductor (L) and a capacitor (C).
The "LC filter circuit" is shown connected in series with the primary of a
transformer (T) across an incoming main (an AC power line?). The secondary
of the transformer (T) is shown connected across the input of a bridge
rectifier of a (capacitor-input-type) DC power supply (C and Co). It is
indicated that.
"(t)he resonant frequency of the LC circuit is chosen to reduce
overvoltage peaks and improve the current phase angle. Usually the
frequency is the fifth but maybe the ninth or thirteenth harmonic of the
mains frequency."
The Japanese patent 58[1983]-163271 of Kawaguchi Yuuji et al shows (in FIG.
1) what is referred to (in the Abstract) as a "filter circuit" (7). The
"filter circuit"includes the parallel combination of an inductor (2) and a
capacitor (3). The "filter circuit" (7) is shown connected to couple the
input of a (capacitor-input-type) DC power supply (of an "inverter unit")
(8) to a "commercial power supply" (AC power line?) (1). It is indicated
(in the Abstract) that the "filter circuit" is
"(t)o reduce the third and fifth harmonic waves due to capacitor charge
improving power factor . . . ."
Further, it is indicated (in the body of the patent) that the "filter
circuit" is resonant at the third harmonic. The Q was not specified.
Finally, it is indicated (in the body of the patent) that
"the power factor can be improved by a large margin to 90%, as compared to
64% when the filter of this invention is not inserted."
The Japanese patent 56[1981]-157261 of Kouichi Noguchi shows (in FIG. 3)
what is referred to (in the Abstract) as an "overcurrent limiting
capacitor" (10) and three "parallel resonant circuits" (16, 17, and 20).
Each "parallel resonant circuit" includes the parallel combination of an
inductor and a capacitor (the inductor of "circuit" 16 being designated 15
and the capacitor of the "circuit" being designated 14). The "overcurrent
limiting capacitor" (10) and the three "parallel resonant circuits" (16,
17, and 20) are shown connected in series to couple the input of a
(capacitor-input-type) DC power supply (which includes components 12, 11,
and 13) to an "AC power source (9). As to the resonant frequency of the
"circuits", it is indicated that
"harmonic components generated due to the distortion of the waveform at
the time of charging voltage rise are suppressed by the circuits 16-20 set
to have high impedance against the frequency. When the interval of the
resonance frequency of the resonance circuit is set as narrow as possible
to increase the frequency, its effect can be increased."
To illustrate the operation of series-connected, parallel-resonant "LC
filters" of the type shown in the three, above-mentioned, prior-art
patents, performance characteristics were calculated for a number of
circuits. First, the performance characteristics were calculated for a
circuit in which a (capacitor-input-type) DC power supply was directly
connected (zero (0) "LC-filters") to an AC power line, as was previously
discussed. Then, the performance characteristics were calculated for a
circuit in which the DC power supply was coupled to the AC power line by
means of a number of (series-connected, parallel-resonant) "LC filters."
Calculations were performed for a circuit in which the DC power supply was
coupled to the AC power line by means of one (1) (parallel-resonant) "LC
filter", resonant at the third harmonic of the AC power line frequency.
Next, calculations were performed for a circuit in which the DC power
supply was coupled to the AC power line by means of two (2)
(series-connected, parallel-resonant) "LC filters", resonant at the third
and fifth harmonics of the AC power line frequency. Then, three (3) "LC
filters" were used, resonant at the third, fifth, and seventh harmonics;
four (4) "LC filters" were used, resonant at the third, fifth, seventh,
and ninth harmonics; five (5) "LC filters" were used, resonant at the
third, fifth, seventh, ninth, and eleventh harmonics; and, six (6) "LC
filters" were used, resonant at the third, fifth, seventh, ninth,
eleventh, and thirteenth harmonics. The "LC filters" had a Q of 1/2, as
employed (below) in the present invention. Again, small resistors were
included in series with various components to facilitate the calculations.
A constant, 100 watt load was used, for reasons which will become apparent
shortly. For the six (6) "LC filter" circuit, performance characteristics
were calculated at various AC power line frequencies. At a frequency of 57
Hz, the DC potential developed across the load collapsed.
______________________________________
Harmonic currents generated on an AC power line by a DC
power supply coupled to the line by a number of series-
connected, parallel-resonant "LC filters"
Number of Output
"LC filters"
Power Frequency Voltage Distortion
______________________________________
0 131 W 60 Hz 162 V DC 157%
1 100 W 60 Hz 137 V DC 32%
2 100 W 60 Hz 130 V DC 15%
3 100 W 60 Hz 127 V DC 9%
4 100 W 60 Hz 121 V DC 6%
5 100 W 60 Hz 113 V DC 4.4%
6 100 W 60 Hz 102 V DC 3.1%
6 100 W 57 Hz * *
6 100 W 59 Hz 99 V DC 3.3%
6 100 W 61 Hz 107 V DC 3.8%
6 100 W 62 Hz 112 V DC 5.8%
6 100 W 63 Hz 119 V DC 9.3%
______________________________________
It is important to note the relatively low DC potential which was developed
across the load, as compared to the 162 volt DC potential which was
developed by the DC power supply across the load without the "LC filters".
Also, it is important to note the sensitivity of the DC load potential to
frequency.
The above-mentioned, series-connected, parallel-resonant "LC filters" form
a simple series (loop) circuit with the generator of the AC power line and
the input (of the bridge rectifier) of the DC power supply. As a
consequence, the waveform of the current flowing through the input (of the
bridge rectifier) of the DC power supply must be the same as the waveform
of the current flowing through the generator of the AC power line. From
the sinusoidal voltage waveform developed across the AC power line, the
"LC filters" develop across the input (of the bridge rectifier) of the DC
power supply a trapezoidal (near square-wave) voltage waveform having a
peak level, which is just slightly greater that the level developed at the
output of the DC power supply.
Disclosed in the British patent 1,472,411 of T. Kennedy is a filter network
which is for use with a load having a non-linear control device (saturable
reactor) and which is for absorbing unwanted harmonic currents. The filter
network employs a plurality of filters each including an inductor and a
capacitor which is connected in series with the (associated) inductor.
Each of the filters (inductor-capacitor combinations) is connected in
parallel with the load. An additional inductor is employed connected
between the AC power line and the load to couple the load to the AC power
line. It is indicated (on page 2 in lines 113-115 of the T. Kennedy
patent) that each of the filters (inductor-capacitor combinations) is
tuned to a frequency less than the harmonic frequency which it is to
filter. Further, it is indicated (on page 3 in lines 115-128) that
". . . the existence of harmonics in the line makes it not only
impractical, but also impossible to filter out all of the harmonic
current. An attempt to do so may result in overloading the filters.
Accordingly, it has been determined that the better approach is to remove
only a percentage of the harmonic currents generated as a result of the
load and control device. Thus, a certain amount of harmonic current is
reflected back into the supply line. The amount of harmonic current so
reflected can be adjusted depending upon the requirements of the utility
system supplying power."
In an example in the T. Kennedy patent it is indicated (on page 4 in lines
109-112) that 70 percent of the harmonic currents are removed and 30
percent of the harmonic currents are reflected into the AC power line.
Further, it is indicated (on page 4 in lines 112-115) that
"(i)f the utility requirements on harmonics are more severe, it is
possible to remove an even higher percentage such as 75%."
Although of some value in reducing the level of some of the harmonic
currents, it is important to note that the reductions in the levels of
harmonic currents afforded by the network disclosed in the above-mentioned
T. Kennedy patent does not approach that required to meet the above
mentioned standard.
In the U.S. Pat. No. 4,222,096 of D. Capewell and the U.S. Pat. No.
4,369,490 of F. Blum a circuit is disclosed which includes a capacitor
connected in parallel with the input of the bridge rectifier of a
(capacitor-input-type) DC power supply and an inductor connected between
the AC power line and the input of the rectifier to couple the DC power
supply to the AC power line. In the F. Blum patent it is indicated (on
column 5 in lines 23-29) that without the above-mentioned circuit, the DC
power supply was found to present a power factor of 65 percent to the AC
power line. Also, it was found that without the above-mentioned circuit,
the level of the third harmonic current was 88 percent, the level of the
fifth harmonic current was 65 percent, and the level of the seventh
harmonic current was 38 percent of the level of the fundamental current.
In one example, With the above-mentioned circuit, the DC power supply was
found to present a power factor of 94 percent to the AC power line. Also,
with the above-mentioned circuit, the level of the third harmonic current
was 20 percent, the level of the fifth harmonic current was 6 percent, and
the level of the seventh harmonic current was 2 percent of the level of
the fundamental current.
Although the above-mentioned circuit greatly increases the power factor a
DC power supply presents to an AC power line and greatly reduces the
levels of the harmonic currents, It is important to note that the DC power
supply (and circuit combination) still does not even come close to meeting
the above-mentioned military standard.
The U.S. Pat. No. 3,461,372 of Clive Pickup et al. shows (in the sole
figure) what is referred to in the Patent as a "D.C. to A.C. power
converter". Shown is a switching transistor (3) configured to alternately
switch on and off power from a DC source (Vc) responsive to a square wave
(1-2), a plurality of series resonant "circuits" (4-5, 6-7, and 8-9)
configured to "attenuate" lower even harmonics, and a plurality of
parallel resonant "circuits" (10-11, 12-13, and 14-15) configured to
"block" odd harmonics, the combination to provide a sinusoidal output
across a load (R1). More specifically, the collector of the transistor (3)
is coupled to the D.C. source (Vc) by an inductance (Lf). Further, the
plurality of series resonant "circuits" (4-5, 6-7, and 8-9) are each
connected between the collector and the emitter of the transistor (3).
Finally, the plurality of parallel resonant "circuits" (10-11, 12-13, and
14-15) are connected between the collector and the output. It is indicated
(in column 2, lines 39-41) that the plurality of series resonant
"circuits" (4-5, 6-7, and 8-9) are each tuned to a different even harmonic
(2f. 4f. and 6f being shown in the figure). Further, it is indicated (in
column 2, lines 41-44) that the inductance (Lf) is parallel resonant at
the driving frequency with the effective capacitance of all the series
resonant "circuits" (4-5, 6-7, and 8-9). Finally, it is indicated (in
column 2, lines 44-47) that the parallel resonant "circuits" are resonant
at the odd order harmonics (3f, 5f, and 7f being shown in the figure). It
is important to note that the C. Pickup, et al Patent does not pertain to
D.C. power supplies nor power factor, let alone the power factor a D.C.
power supply presents to an AC power line.
Performance characteristics were calculated for a circuit in which a
(capacitor-input-type) DC power supply was coupled to an AC power line by
means of three parallel-resonant series-connected inductor-capacitor-type
"circuits", which were, respectively, resonant at the third, the fifth,
and the seventh harmonic frequencies of the AC power line frequency. In
addition, three series-resonant shunt-connected inductor-capacitor-type
"circuits" were connected across the AC power line, which were,
respectively, resonant at the second, the fourth, and the sixth harmonic
frequencies of the AC power line frequency. Finally, connected across the
AC power line, was an inductor, having an inductance chosen to parallel
resonant at the power line frequency with the effective capacitance of all
the series resonant "circuits". The three parallel-resonant series-connect
inductor-capacitor-type "circuits" had a Q of 1/2; and, the three
series-resonant shunt-connected inductor-capacitor-type "circuits" had a Q
of one, as employed (below) in the present invention. A sine wave AC power
line potential; and, a 144 ohm load were used. Again, as previously
indicated, small resistors were included in series with various components
to facilitate the calculations. The total harmonic distortion was reduced
to 15.6%. However, it is important to note the DC power supply only
developed a DC potential of 122 volts across the load, as compared to the
162 volt DC potential which was developed by the DC power supply across
the 200 ohm (131 watt) load when directly connected across the AC power
line.
Next, the performance characteristics were calculated for a circuit in
which the DC power supply was coupled to the AC power line by means of a
network which includes various parallel-resonant series-connected
inductor-capacitor-type "circuits" and various series-resonant
shunt-connected inductor-capacitor-type "circuits". The "circuits" were
all resonant at odd harmonic frequencies of the AC power line frequency
(third, fifth, seventh, etc.).
__________________________________________________________________________
Harmonic currents generated on an AC power line by a DC
power supply coupled to the line by a number of series-
connected parallel-resonant "circuits", a number of series-
resonant "circuits" being connected across the AC power line.
# of # of
series
parallel
resonant
resonant Output
circuits
circuits
Load Power
Freq.
Voltage
Dist.
__________________________________________________________________________
0 0 200
Ohms
131 W
60 Hz
162 V DC
157%
1 1 200
Ohms
97 W
60 Hz
139 V DC
47%
1 1 100
W 100 W
60 Hz
138 V DC
49%
2 2 200
Ohms
87 W
60 Hz
132 V DC
43%
2 2 100
W 100 W
60 Hz
131 V DC
39%
3 3 200
Ohms
85 W
60 Hz
130 V DC
44%
3 3 100
W 100 W
60 Hz
127 V DC
40%
4 4 200
Ohms
81 W
60 Hz
127 V DC
46%
4 4 100
W 100 W
60 Hz
120 V DC
43%
5 5 200
Ohms
77 W
60 Hz
124 V DC
47%
5 5 100
W 100 W
60 Hz
103 V DC
45%
6 6 200
Ohms
73 W
60 Hz
121 V DC
48%
6 6 100
W 100 W
60 Hz
103 V DC
48%
__________________________________________________________________________
Again, it is important to note the relatively low DC potential which was
developed across the load, as compared to the 162 volt DC potential which
was developed by the DC power supply across the 200 ohm (131 watt) load
when directly connected across the AC power line (zero (0) "LC-filters").
Further, it is important to note the relatively poor regulation provided.
Also, it is interesting to note that the level of certain harmonics
increased as additional "circuits" were added.
The German patent (Offenlegungsschrift, 1,927,415, Jan. 2, 1979) of Hemesh
Laxmidas Thanawala dated Jan. 2, 1970, "concerns an arrangement for
high-voltage direct-current-transmission by connecting an
alternating-current-network with a direct-current-network over a static
frequency-changer and a transformer." Apparently, the object of the
invention is to provide a "filter" permitting the reduction of the leakage
inductance (and, thus, the size) of the transformer and the size of the
thyratron tubes. shown in block form are (just) two basic topologies.
However, each block is to be replaced by one, or more, networks chosen
from thirteen basic resistor-capacitor-inductor networks, which are, also,
shown.
More specifically, FIGS. 1a, 1b, and 2 are similar, FIGS. 1a and 1b taking
an abstract form and FIG. 2 taking a combined schematic and block form.
Each of these figures (FIGS. 1a, 1b, and 2) shows the combination of a
three-phase network (1), a transformer (2), and a static rectifier (3),
which is coupled to the network by the transformer. In addition, FIGS. 1a
and 1b show a block labeled "F" (4); and, FIG. 2 show three blocks, which
are respectively labeled "Fa", "Fb", and "Fc". In FIG. 1a, the block
labeled "F" (4) is shown connected between the three-phase network (1) and
a point "E", having earth potential; and, in FIG. 1b, the block labeled
"F" (4) is shown connected between the transformer (2) and point "E". In
FIG. 2, each of the blocks ("Fa", "Fb", and "Fc") is shown connected
between a respective line of the three-phase network and point "E". In
other words, the block(s) are connected in a simple "shunt" configuration.
The blocks labeled "F" (4) and "Fa", "Fb", and "Fc" are referred to as
"parallelfilters".
FIGS. 6 and 7 of the Thanawala patent are similar, FIG. 6 taking an
abstract form and FIG. 7 taking a combined schematic and block form.
Again, FIGS. 6 and 7 each shows the combination of a three-phase network
(1), a transformer (2), and a static rectifier (3), which is connected to
the transformer. However, FIGS. 6 shows three blocks, which are
respectively labeled "F3", "F2", and "F1". The three blocks ("F3", "F2",
and "F1") are connected in a "pi" configuration. Specifically, the block
labeled "F3" is connected between the three-phase network (1) and the
transformer (2). The block labeled "F2" is connected between the
three-phase network (1) and point "E"; and, block labeled "F1" is
connected between the transformer (2) and point "E". FIGS. 7 shows three
sets of three blocks, which are, again, respectively, labeled "F3", "F2",
and "F1". Each set of three blocks ("F3", "F2", and "F1") is connected in
the "pi" configuration, one set for each line of the three-phase network
(1). The blocks labeled "F3" are referred to both as "rejector-circuits"
and as "filters"; and, the blocks labeled "F2" and "F1" are, again,
referred to as "parallelfilters".
For use in the "filter" blocks, the Thanawala patent shows thirteen basic
resistor-capacitor-inductor sub-networks. Shown in FIG. 3a of the
Thanawala patent is the series combination of a capacitor, an inductor and
a resistor; the series combination of a capacitor and a resistor is shown
in FIG. 3b; a capacitor connected in series with an inductor, which is
connected in parallel with a resistor, is shown in FIG. 3c; in FIG. 3d a
capacitor is shown connected in series with an inductor, which is
connected in parallel with the series combination of another capacitor and
a resistor; and just a single capacitor is shown in FIG. 3e. In FIG. 5a of
the Thanawala patent is shown the parallel combination of a capacitor, an
inductor and a resistor; the parallel combination of a capacitor and a
resistor is shown in FIG. 5b; a capacitor connected in series with a
resistor, which is connected in parallel with an inductor, is shown in
FIG. 5c; in FIG. 5d an inductor is shown connected in parallel with the
series combination of a capacitor and the parallel combination of an
inductor and a resistor; and just a single inductor is shown in FIG. 5e.
FIG. 9a shows the series combination of an inductor and a capacitor, the
combination connected in parallel with the series combination of another
capacitor and a resistor. In FIG. 9b a capacitor is shown connected in
series with an inductor, which is connected in parallel with the series
combination of another capacitor and a resistor. Finally, in FIG. 9c, a
capacitor is shown connected in parallel with a block.
In the translation, it is indicated that the "filter" block sub-networks
(shown in FIGS. 3a-3e, 5a-5e, and 9a-9c of the Thanawala patent) are tuned
to the "harmonics one wants to suppress" (page 3, line 2, of the
translation). Further, it is indicated that the "F1" block is for "drawing
away the harmonics from point C . . . to earth" (page 2, line 37, of the
translation); that the "F2" block is for "drawing away the harmonics from
point C . . . to earth" (page 2, line 38, of the translation); and, that
the "F3" block is for "suppressing undesirable harmonics" (page 2, line
52, to page 3, line 1, of the translation). As an example, it is indicated
(page 2, lines 43-50, of the translation) that the three sub-networks
(parallel branches) shown in FIG. 4 can be tuned to the 5th, 7th, and 11th
"or a higher harmonic". In other words, the "filter" block sub-networks
are tuned to the ODD harmonics, including the the "filter" block
sub-networks shown in FIGS. 3a-3e.
It is important to note how many different configuration are encompassed by
the Thanawala patent. Considering only one phase of the three phases of
the structure shown in block form in FIG. 7 (of the Thanawala patent) and
considering only the choices shown in FIGS. 3a-3e, 5a-5e and 9a-9c, "F1"
can have at least three sub-networks (as shown in FIG. 4) each chosen from
one of the five choices shown in FIGS. 3a-3e; "F2" can have at least one
sub-network chosen from the five choices shown in FIGS. 3a-3e; and, "F3"
can have at least two sub-networks (as shown in FIG. 8) each chosen from
one of the eight choices shown in FIGS. 5a-5e and 9a-9c. In other words,
there are, approximately, (5)(5)(4)(5)(8)(8) or (32,00) choices for one
phase of FIG. 7 alone. In addition, each of these sub-networks can be
tuned to different harmonics. Considering only the 3rd, 5th, 7th, 9th,
11th, and 13th harmonics, there are six choices for each sub-network,
(5)(6)(5)(6)(4)(6)(5)(6)(8)(6)(8)(6) or (1,492,992,000) choices. Further,
each of these sub-networks can have a different Q.
Further, it is important to note that Thanawala considers the various
blocks to be "filters"; and, thus, teaches that filter considerations
should be employed in selecting, tuning and choosing the Q of the various
sub-networks (shown in FIGS. 3a-3e, 5a-5e, and 9a-9c of the patent).
In a more modern system, the "pi" filter of the Thanawala patent is
problematic in that "filter" block "F2" is connected directly across the
AC power line. As connected, this "filter" block presents a low impedance
to harmonics generated elsewhere in the AC power system. Consequently, the
"filter" block is subject to overload.
For purposes herein, it is important to note that none of the topologies
shown in the Thanawala patent (neither the simple shunt topology shown in
FIGS. 1a, 1b, and 2, nor the "pi" topology shown in FIGS. 6 and 7) are the
same as any of the topologies of the present invention. Further, none of
the sub-networks of FIGS. 3a-3e, or any of the other figures shows a
simple series connected inductor-capacitor network, as employed in the
"resonators" of the present invention. Further, none of the sub-networks
of FIGS. 5a-5e, or any of the other figures shows a simple parallel
connected inductor-capacitor network, as employed in the principal
"reflectors" of the present invention.
The reader may also find of interest, the U.S. Pat. No. 2,138,996 of Alan
D. Blumlein; the U.S. Pat. No. 2;008,515 of Walter Plathner et al; the
U.S. Pat. No. 4,591,963 of Daniel D. Retotar; the British patent 221,850
of Ernest Y. Robinson; the German patent 659,504; the article entitled
"Filter Design Simplified" by Berthold Sheffield from Audio Engineering
Vol. 35, No. 5, pages 26, 28, and 58; and the article entitled
"Computer-Aided, Lumped-Element Filter Design and Analysis" by A. Kwon
from Microwave Journal March 1976, pages 53, 54, and 57.
SUMMARY OF THE PRESENT INVENTION
It is therefor the primary object of the present invention to provide a
means by which DC power supplies may be made to meet the
DOD-STD-1399(NAVY) SECTION 300 1 AUG. 1978 standard.
Another object of the present invention to provide a means by which DC
power supplies may be made to meet commercial/industrial standards.
Another object of the present invention is to provide a means by which the
levels of harmonic currents generated on an AC power line by a DC power
supply may be reduced, without appreciably degrading the performance of
the DC power supply.
Still another object of the present invention is to provide a means by
which the power factor a DC power supply presents to an AC power line may
be improved, without appreciably degrading the performance of the DC power
supply.
Briefly, the presently preferred embodiment of the present invention
employs, in combination, at least one "resonator", which is connected
across the input of a DC power supply, and at least one "reflector", which
is connected to couple the input of the DC power supply to an AC power
line. Each "resonator", includes the series combination of an inductor and
a capacitor. At least some of the "reflectors" include the parallel
combination of an inductor and a capacitor. (In FIG. 2, the sole
"resonator" includes inductor 170 and capacitor 172; and, one of the two
"reflectors" includes inductor 150 and capacitor 152.) The "resonator(s)"
provide(s) the harmonic currents which the DC power supply requires for
proper operation; and, the "reflector(s)" reflect(s) the harmonic energy
back toward the power supply. In order to attenuate the level of higher
order harmonic currents, in some embodiments, a "reflector" is employed
which includes, at least, an inductor and a resistor. (In FIG. 2, such a
"reflector" includes inductor 140 and resistor 144.) The number of
"resonators" and the number of "reflectors" vary with the application. In
many applications, only one "resonator" and one "reflector" are required.
However, all applications require at least one of each.
These and other objects of the present invention will no doubt be obvious
to those skilled in the art after having read the following detailed
description of the presently preferred embodiments which are illustrated
in the several figures of the drawing.
IN THE DRAWING
FIG. 1 is a schematic diagram of an embodiment in accordance with the
present invention of a three-phase harmonic currents isolating network for
military applications;
FIG. 2 is a schematic diagram of the presently preferred embodiment in
accordance with the present invention of a harmonic currents isolating
network for commercial/industrial applications;
FIG. 3 is a schematic diagram of a harmonic currents isolating network for
more stringent commercial/industrial applications;
FIG. 4 is a schematic diagram of a three "reflector" harmonic currents
isolating network in accordance with the present invention; and
FIG. 5 is a diagram illustrating a number of the waveforms associated with
the three "reflector" harmonic currents isolating network shown in FIG. 4.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
In accordance with the present invention, illustrated in FIG. 1 of the
drawing generally designated by the number 10 is an embodiment of a
three-phase, military grade network for isolating from an AC power line
the harmonic currents generated by a DC power supply. Also illustrated
with network 10 is a (three phase) AC power line, generally designated 12,
and a (capacitor-input-type) DC power supply, generally designated 14.
Network 10 is shown to employ three terminals (nodes), respectively
designated 20, 20', and 20", each for connection to a respective conductor
of AC power line 12 and three terminals (nodes), respectively designated
22, 22', and 22", each for connection to DC power supply 14.
Network 10 also employs three similar portions, respectively designated 30,
30', and 30", each connected between a respective one of terminals 20,
20', and 20" and a respective one of terminals 22, 22', and 22". (Herein,
similar one of terminals 22, 22', and 22". (Herein, similar
portions/components are similarly numbered.) Additionally, network 10
employs three similar portions, respectively designated 32, 32', and 32",
each connected between a respective pair of terminals 20 and 20', 20' and
20", and 20" and 20.
Portion 30 includes an inductor (choke) 40 which is connected between
terminal 20 and a node 42. Additionally, portion 30 includes a resistor 44
and a capacitor 46 which are connected in series between terminal 20 and
node 42. Further, portion 30 includes an inductor 50 and a capacitor 52,
the combination (of inductor 50 and capacitor 52) being connected in
parallel (parallel resonant) between node 42 and a node 54. Finally,
portion 30 includes an inductor 58 and a capacitor 60, the combination (of
inductor 58 and capacitor 60) being connected in parallel (parallel
resonant) between node 54 and terminal 22.
Portion 32 includes an inductor 70 and a capacitor 72, the combination (of
inductor 70 and capacitor 72) being connected in series (series resonant)
between terminals nodes 22 and 22'.
DC power supply 14 employs a bridge rectifier 80 and a filter capacitor 82.
The input of rectifier 80 is connected to terminals 22, 22', and 22"; and,
the output of the rectifier is (in this case) directly connected across
capacitor 82 (between a pair of terminals 84 and 86) to develop a DC
(output) potential (between the terminals) across the capacitor. A load
(for DC power supply 14) is represented by a resistor 90 connected between
terminals 84 and 86. Bridge rectifier 80 includes three rectifier diodes
(not shown) each having a cathode coupled to terminal 84 and an anode
coupled to a respective one of terminals 22, 22', and 22". Further, bridge
rectifier 80 includes three more diodes (also not shown) each having an
anode coupled to terminal 86 and a cathode coupled to a respective one of
terminals 22, 22', and 22".
The inductor (70, 70', or 70") and capacitor (72, 72', or 72") combination
of each of portions 32, 32', and 32" form (what is referred to herein as)
a "resonator" for (in conjunction with power supply 14) generating
harmonic currents for the power supply. In the presently preferred
embodiment, the inductance of the inductor (70, 70', or 70") and the
capacitance of the capacitor (72, 72', or 72") are chosen such that each
inductor-capacitor combination resonates at a frequency near the twelfth
harmonic frequency of the power-line frequency and has a Q of
approximately one.
The inductor-capacitor combinations of portion 30 (40 and 46, 50 and 52,
and 58 and 60) (as well as the similar combinations of portions 30' and
30") form (what is referred to herein as) "reflectors" for (it is
believed) coupling energy at the AC power line frequency from AC power
line 12 to the "reflector(s)" and DC power supply 14 and for reflecting
harmonic energy back toward the power supply. In the presently preferred
embodiment, inductor 58 and capacitor 60 resonate near the seventh
harmonic frequency; inductor 50 and capacitor 52 resonate near the fifth
harmonic frequency; and, inductor 40 and capacitor 46 resonate near the
thirteenth harmonic frequency. Each of the inductor-capacitor combinations
of the "reflectors" have a Q which is in the range of 0.5 to 3. It is
important to note that to attenuate the level of higher order harmonic
currents, a resistor (44) is included in series with the capacitor (46) in
the highest frequency "resonator". The resistor (44) resistance is
approximately equal to the characteristic impedance of each of the
"resonators" (each of portions 32, 32', and 32"). Finally, it is important
to note that no inductor-capacitor combination resonates at an exact
multiple of the resonate frequency of another inductor-capacitor
combination; because, it has been observed that certain combinations of
frequency and Q have resulted in excessive levels of harmonic currents in
the line.
In the presently preferred embodiment, the following component values are
employed for the three-phase, military guide network shown in FIG. 1:
______________________________________
inductor 40 2.41 mH,
resistor 44 12 ohms,
capacitor 46 23.2 mfd,
inductor 50 2.84 mH,
capacitor 52 97.4 mfd,
inductor 58 2.43 mH,
capacitor 60 46.9 mfd,
inductor 70 3.55 mH,
capacitor 72 10.95 mfd,
capacitor 82 3000 mfd, and
resistor 90 a constant 2000 watt load (such as is
presented by a switching power
supply and its load).
______________________________________
The following performance characteristics were calculated for the
three-phase, military grade network shown in FIG. 1 by means of the
above-mentioned computer:
______________________________________
57 Hz 60 Hz 63 Hz
______________________________________
level of the harmonic currents relative the fundamental
5th 1.75% 0.73% 2.10%
7th 2.85% 1.78% 1.10%
11th 1.71% 1.42% 1.66%
13th 1.30% 0.79% 0.68%
17th 0.96% 0.84% 0.57%
23rd 0.49% 0.87% 0.58%
25th 0.16% 0.38% 0.49%
total harmonic distortion
4.12% 2.82% 3.12%
phase angle in degrees
14 leading 13 leading 15 leading
voltage level developed across the load (resistor 90)
144 V DC 144.4 V DC 146.6 V DC
______________________________________
To illustrate the function of the "resonators" (70-72, 70'-72', and
70"-72"), performance characteristics were calculated for the three-phase,
military grade network shown in FIG. 1, WITHOUT the "resonators". At 60
Hz, the voltage level developed across the load (resistor 90) dropped to
119 volts; and, the total harmonic distortion increased to 4.8%. Further,
performance characteristics were calculated for for the three-phase,
military grade network shown in FIG. 1, with the "resonators" RELOCATED to
each be across a respective phase of the AC power line. At 60 Hz, the
voltage level developed across the load (resistor 90), again, dropped to
119 volts; and, the total harmonic distortion increased to 4.9%. Finally,
to illustrate the function of the resistors (44, 44', and 44"),
performance characteristics were calculated for the three-phase, military
grade network shown in FIG. 1, WITHOUT the resistors.
The following performance characteristics were calculated for the
three-phase, military grade network shown in FIG. 1 WITHOUT the resistors:
______________________________________
57 Hz 60 Hz 63 Hz
______________________________________
level of the harmonic currents relative the fundamental
5th 1.77% 0.59% 2.07%
7th 2.47% 1.61% 1.04%
11th 0.36% 0.13% 0.02%
13th 0.30% 0.24% 0.02%
17th 0.81% 1.06% 0.62%
23rd 1.28% 2.09% 1.65%
25th 1.42% 2.26% 1.84%
29th 1.59% 1.99% 1.62%
31st 1.66% 1.80% 1.49%
35th 1.25% 1.05% 0.83%
37th 1.04% 0.72% 0.57%
49th 0.57% 0.46% 0.56%
61st 0.37% 0.17% 0.28%
total harmonic distortion
4.89% 5.05% 4.49%
voltage level developed across the load (resistor 90)
144 V DC 144.4 V DC 146.6 V DC
______________________________________
Turning now to FIG. 2, the presently preferred embodiment of a
commercial/industrial grade harmonic currents isolating network is
illustrated generally designated 110. With network 110 is illustrated a
(single phase) AC power line, generally designated 112, and another
(capacitor-input-type) DC power supply, generally designated 114. Network
110 is shown to employ two terminals (nodes), respectively designated 120
and 120', each for connection to a respective conductor of AC power line
112 and two terminals (nodes), respectively designated 122 and 122', each
for connection to DC power supply 114.
Network 110 employs two "reflectors" and one "resonator". The first
"reflector" includes an inductor 140, which is connected between terminal
120 and a node 142. Additionally, the first "reflector" includes a
resistor 144 and a capacitor 146 which is connected in series with
resistor 144 between terminal 120 and node 142. The second "reflector"
includes another inductor 150 and another capacitor 152 which are
connected in parallel between node 142 and terminal 122. Finally, the
"resonator" includes still another inductor 170 and still another
capacitor 172 connected in series between terminals 122 and 122'. Terminal
120' is directly coupled (connected) to terminal 122'.
DC power supply 114 employs a bridge rectifier 180 and a filter capacitor
182. The input of rectifier 180 is connected to terminals 122 and 122';
and, the output of the rectifier is directly connected across capacitor
182 (between a pair of terminals 184 and 186) to develop a DC (output)
potential (between the terminals) across the capacitor. A load (for DC
power supply 114) is represented by a resistor 190 connected between
terminals 184 and 186.
In the presently preferred embodiment, the inductance of the inductor (170)
and the capacitance of the capacitor (172) of the "resonator" are chosen
such that they resonate at a frequency near the sixth harmonic frequency
of the power-line frequency and have a Q of approximately one to generate
currents at both the fifth and the seventh harmonic frequencies.
Additionally, the (inductor 170 and capacitor 172) "resonator" generates
an appreciable amount of third harmonic current without the high no load
voltage characteristic of a "resonator" resonate at a lower frequency. The
"reflector" which includes inductor 150 and capacitor 152 resonates at a
frequency near the fifth harmonic frequency and has a Q of approximately
one. The other "reflector", which includes inductor 140 and capacitor 146,
resonates near the seventh harmonic frequency and has a Q of approximately
3/4. In this embodiment, no "reflector" resonant near the third harmonic
frequency is employed. Rather, at the third harmonic frequency the
off-resonant impedance of the other "reflectors" (150-152 and 140-146) is
considered sufficient for many applications. The resistor (144) resistance
is approximately equal to the characteristic impedance of the "resonator".
In the presently preferred embodiment, the following component values are
employed for the commercial/industrial grade harmonic currents isolating
network shown in FIG. 2:
______________________________________
inductor 140 36 mH,
resistor 144 115 ohms,
capacitor 146 4.84 mfd,
inductor 150 67.2 mH,
capacitor 152 5.08 mfd,
inductor 170 56.5 mH,
capacitor 172 4.27 mfd,
capacitor 182 600 mfd, and
resistor 190 a constant 200 ohm resistive load
consuming approximately 100 watts.
______________________________________
The following performance characteristics were calculated for the
commercial/industrial network shown in FIG. 2:
__________________________________________________________________________
47 Hz 50 Hz 53 Hz 57 Hz 60 Hz 63 Hz
__________________________________________________________________________
level of the harmonic currents relative the fundamental
3rd 34.59% 33.86% 31.13% 19.83% 15.20% 13.20%
5th 2.87% 2.36% 1.10% 0.91% 1.35% 1.01%
7th 0.82% 4.50% 8.76% 9.03% 8.85% 8.14%
9th 3.81% 2.03% 4.57% 4.84% 5.56% 5.85%
11th
4.66% 2.91% 0.91% 0.46% 1.11% 1.72%
13th
3.20% 3.01% 1.11% 1.71% 1.66% 1.44%
15th
1.37% 2.22% 1.61% 1.63% 1.89% 1.95%
17th
0.69% 1.17% 1.48% 0.37% 0.66% 0.89%
19th
1.28% 0.55% 1.01% 0.70% 0.63% 0.54%
power factor
0.91 0.91 0.90 0.89 0.93 0.94
voltage level developed across the load (resistor 190)
134 V DC 135 V DC
138 V DC
143 V DC
144 V DC
143 V DC
__________________________________________________________________________
To illustrate the performance of the commercial/industrial grade harmonic
currents isolating network shown in FIG. 2 as a function of the series
impedance presented by the network to the AC power line at the power line
frequency, computations were performed on variations of the network in
which the inductance (but not the resonant frequency) of the "reflectors"
was changed. First, a "resonator" impedance of 165 Ohms at 5.5 Times the
AC power line frequency was employed; and, next, a "resonator" impedance
of 240 Ohms at 5.5 Times the AC power line frequency was employed. (A
constant, 100 watt, load was employed.) It is important to note how the
power factor improves as the series inductance increases.
______________________________________
Component
Values #1 #2 #3 #4 #5 #6
______________________________________
"Reflector"
(140-144-146)
Resonant 7th 7th 7th 7th 7th 7th
Frequency
(140) in H.
.0134 .0191 .0248 .0306 .0382 .0497
(146) in Mfd
10.70 7.520 5.790 4.700 3.760 2.890
(144) in Ohms
"Reflector"
(150-152)
Resonant 5th 5th 5th 5th 5th 5th
Frequency
(150) in H.
.0134 .0191 .0248 .0306 .0382 .0497
(152) in Mfd
21.00 14.70 11.30 9.210 7.370 5.670
"Resonator"
(170-172)
Resonant 5.5 5.5 5.5 5.5 5.5 5.5
Frequency
(170) in H.
.0796 .0796 .0796 .0796 .0796 .0796
(172) in Mfd
2.920 2.920 2.920 2.920 2.920 2.920
For a "Resonator" Impedance of 165 Ohms at
5.5 Times the AC Power Line Frequency
Performance
Character-
istics
Total Series
.0268 .0382 .0496 .0612 .0764 .0994
Inductance
in Henrys
Average DC
135.0 133.0 133.5 135.5 136.5 140.5
Output
Voltage
in Volts
Power Factor
0.649 0.768 0.825 0.861 0.886 0.917
Harmonic
Levels
3rd 90.0% 65.0% 51.0% 42.0% 33.0% 24.0%
5th 2.3% 1.4% 1.0% 0.9% 0.8% 0.6%
7th 13.0% 17.0% 18.0% 15.0% 12.0% 8.5%
9th 6.0% 4.1% 4.8% 4.5% 4.2% 3.6%
11th 4.8% 5.0% 3.2% 2.6% 1.9% 1.0%
______________________________________
______________________________________
Component
Values #1 #2 #3 #4 #5 #6
______________________________________
"Reflector"
(140-144-146)
Resonant 7th 7th 7th 7th 7th 7th
Frequency
(140) in H.
.0134 .0191 .0248 .0306 .0382 .0497
(146) in Mfd
10.70 7.520 5.790 4.700 3.760 2.890
(144) in Ohms
"Reflector"
(150-152)
Resonant 5th 5th 5th 5th 5th 5th
Frequency
(150) in H.
.0134 .0191 .0248 .0306 .0382 .0497
(152) in Mfd
21.00 14.70 11.30 9.210 7.370 5.670
"Resonator"
(170-172)
Resonant 5.5 5.5 5.5 5.5 5.5 5.5
Frequency
(170) in H.
.1160 .1160 .1160 .1160 .1160 .1160
(172) in Mfd
2.010 2.010 2.010 2.010 2.010 2.010
For a "Resonator" Impedance of 240 Ohms at
5.5 Times the AC Power Line Frequency
Performance
Character-
istics
Total Series
.0268 .0382 .0496 .0612 .0764 .0994
Inductance
in Henrys
Average DC
138.0 133.0 130.5 131.5 132.5 133.5
Output
Voltage
in Volts
Power Factor
0.682 0.751 0.832 0.851 0.886 0.897
Harmonic
Levels
3rd 80.0% 63.0% 50.0% 42.0% 34.0% 27.0%
5th 1.8% 1.2% 0.9% 0.9% 0.9% 0.8%
7th 15.0% 18.0% 20.0% 18.0% 15.0% 11.0%
9th 11.0% 3.0% 4.2% 3.4% 3.1% 2.8%
11th 2.6% 4.6% 3.6% 2.7% 2.0% 1.4%
______________________________________
For more stringent applications, a commercial/industrial grade harmonic
currents isolating network is illustrated in FIG. 3 generally designated
210. Network 210 employs two terminals (nodes), respectively designated
220 and 220', each for connection to a respective conductor of an AC power
line and two terminals (nodes), respectively designated 222 and 222', each
for connection to a DC power supply. Additionally, network 210 employs
five "reflectors" connected in series between terminals 220 and 222 and
two "resonators". The first three "reflectors" include the parallel
connection of an inductor 240 and a resistor 244 in the first; the
parallel connection of an inductor 250 and a capacitor 252 in the second;
and an inductor 258 and a capacitor 260 in the third. Connected between
the third and fourth "reflector", the first "resonator" includes an
inductor 270 and a capacitor 272 connected in series between a node 274
and terminal 222'. The last two "reflectors" include the parallel
combination of an inductor 340 and a capacitor 346 in the fourth and the
parallel connection of an inductor 350 and a capacitor 352 in the fifth.
Finally, the last (second) "resonator" includes an inductor 370 and a
capacitor 372 connected in series between terminals 222 and 222'. Terminal
220' is directly coupled (connected) to terminal 222'.
In the presently preferred embodiment, the following component values are
employed for the commercial/industrial grade harmonic currents isolating
network illustrated in FIG. 3:
______________________________________
inductor 240
30 mH,
resistor 244
115 ohms,
inductor 250
30.5 mH,
capacitor 252
9.23 mfd, freq. 5th harmonic, Q
1/2,
inductor 258
21.8 mH,
capacitor 260
6.59 mfd, freq. 7th harmonic, Q
1/2,
inductor 270
102 mH,
capacitor 272
7.66 mfd, freq. 3rd harmonic, Q
1,
inductor 340
16.9 mH,
capacitor 346
5.12 mfd, freq. 9th harmonic, Q
1/2,
inductor 350
13.9 mH,
capacitor 352
4.19 mfd, freq. 11th harmonic, Q
1/2,
inductor 370
51 mH, and
capacitor 372
3.84 mfd, freq. 6th harmonic, Q
1,
______________________________________
a DC power supply capacitor capacitance of 600 mfd, and a constant 200 ohm
resistive load consuming approximately 100 watts.
The following performance characteristics were calculated for the
commercial/industrial grade harmonic currents isolating network
illustrated in FIG. 3:
______________________________________
57 Hz 60 Hz 63 Hz
______________________________________
level of the harmonic currents relative the fundamental
3rd 7.89% 1.03% 6.60%
5th 1.12% 0.42% 2.74%
7th 0.42% 0.21% 0.36%
9th 1.52% 0.32% 1.91%
11th 0.89% 0.37% 0.89%
13th 2.07% 0.74% 1.17%
15th 3.64% 1.78% 2.26%
17th 1.39% 2.02% 1.88%
19th 1.55% 0.82% 1.97%
21st 0.79% 0.68% 1.15%
23rd 0.93% 0.56% 0.75%
25th 0.62% 0.19% 0.99%
27th 0.55% 0.47% 2.00%
29th 0.50% 0.44% 1.50%
31st 0.30% 0.38% 0.26%
total harmonic distortion
9.55% 3.37% 8.87%
voltage level developed across the load
156 V DC 147.5 V DC 147 V DC
______________________________________
To illustrate the function of the "resonator" (270-272 and 370-372),
performance characteristics were calculated for the commercial/industrial
grade harmonic currents isolating network shown in FIG. 3, WITHOUT the
"resonators". At 57 Hz, the voltage level developed across the load
dropped to 115 volts; and, the total harmonic distortion increased to
35.2%. Next, at 60 Hz, the voltage level developed across the load dropped
to 118 volts. Then, at 63 Hz, the voltage level developed across the load
dropped to 121 volts; and, the total harmonic distortion increased to
33.5%. Further, performance characteristics were calculated for the
commercial/industrial grade harmonic currents isolating network shown in
FIG. 3, with the "resonators" RELOCATED to each be across the AC power
line. At 57 Hz, the voltage level developed across the load dropped to 115
volts; and, the total harmonic distortion increased to 30.1%. Next, at 60
Hz, the voltage level developed across the load dropped to 118 volts; and,
the total harmonic distortion increased to 34.1%. Then, at 63 Hz, the
voltage level developed across the load dropped to 121 volts. Finally, to
illustrate the function of the resistor (244), performance characteristics
were calculated for the commercial/industrial grade harmonic currents
isolating network shown in FIG. 3, WITHOUT the resistor.
The following performance characteristics were calculated for the
commercial/industrial grade harmonic currents isolating network
illustrated in FIG. 3 WITHOUT the resistor (244):
______________________________________
57 Hz 60 Hz 63 Hz
______________________________________
level of the harmonic currents relative the fundamental
3rd 7.14% 0.29% 6.30%
5th 1.31% 0.81% 2.02%
7th 0.07% 0.30% 0.23%
9th 1.76% 0.27% 1.83%
11th 0.91% 0.32% 0.47%
13th 1.73% 1.69% 2.57%
15th 1.92% 6.15% 5.73%
17th 5.58% 2.33% 6.29%
19th 4.33% 3.20% 0.30%
21st 0.69% 0.50% 1.07%
23rd 1.18% 0.52% 0.63%
25th 0.34% 0.86% 0.65%
27th 0.68% 0.30% 0.10%
29th 0.25% 0.56% 0.70%
31st 0.40% 0.12% 0.20%
total harmonic distortion
11.44% 7.82% 11.47%
voltage level developed across the load
115 V DC 118 V DC 121 V DC
______________________________________
In another embodiment, inductor 270 and capacitor 272 (of the first
"resonator") are connected in series between terminal 222' and a node 400
at the juncture of inductors 340 and 350.
Turning now to FIG. 4, a three "reflector" harmonic currents isolating
network is illustrated generally designated 510. With network 510 is
illustrated a (single phase) AC power line, generally designated 512, and
another (capacitor-input-type) DC power supply, generally designated 514.
Network 510 is shown to employ two terminals (nodes), respectively
designated 520 and 520', each for connection to a respective conductor of
AC power line 512 and two terminals (nodes), respectively designated 522
and 522', each for connection to DC power supply 514.
Network 510 employs three "reflectors" and one "resonator". The first
"reflector" includes an inductor 540, which is connected between terminal
520 and a node 542. Additionally, the first "reflector" includes a
resistor 544 and a capacitor 546 which is connected in series with
resistor 544 between terminal 520 and node 542. The second "reflector"
includes another inductor 550 and another capacitor 552 which is connected
in parallel with inductor 550 between node 542 and a node 642. The third
"reflector" includes yet another inductor 650 and another capacitor 652
which is connected in parallel with inductor 650 between node 642 and
terminal 522. The "resonator" includes still another inductor 670 and
still another capacitor 672 connected in series between terminals 522 and
522'. Terminal 520' is directly coupled (connected) to terminal 522'.
Further, this embodiment of the harmonic currents isolating network
employs a "damping" network connected in parallel with the "resonator".
Specifically, the "damping" network includes a resistor 674 and a
capacitor 676, which is connected in series with the resistor (674)
between terminals 522 and 522'.
DC power supply 514 employs a bridge rectifier 680 and a filter capacitor
682. The input of rectifier 680 is connected to terminals 522 and 522';
and, the output of the rectifier is directly connected across capacitor
682 (between a pair of terminals 684 and 686) to develop a DC (output)
potential (between the terminals) across the capacitor. Although a load
(for DC power supply 514) is represented by a resistor 690 connected
between terminals 684 and 686, for the following calculations, a constant,
100 watt load was employed, such as a switching regulator represents.
In the presently preferred embodiment, the inductance of the inductor (670)
and the capacitance of the capacitor (672) of the "resonator" are chosen
such that they resonate at a frequency near the sixth harmonic frequency
of the power-line frequency. The "reflector" which includes inductor 650
and capacitor 652 resonates at a frequency near the third harmonic
frequency; resonant at a frequency near the fifth harmonic frequency is
the "reflector" which includes inductor 550 and capacitor 552; and, the
other "reflector", which includes inductor 540 and capacitor 546,
resonates near the seventh harmonic frequency. The resistor (544)
resistance is approximately equal to the characteristic impedance of the
"resonator". For the "damping" network, the resistor (674) resistance and
the capacitor (676) capacitance are chosen to reduce the amplitude of
harmonics having a frequency high than the resonant frequency of the
highest frequency "reflector", with due regard to the increased power
loss. Preferably, these components are chosen to critically damp the
equivalent series circuit consisting of the "resonator" inductance, the
damping resistor and the series combination of the "resonator" and
"damping" network capacitances.
To illustrate the performance of the harmonic currents isolating network
shown in FIG. 4 as a function of the series impedance presented by the
network to the AC power line at the power line frequency, computations
were performed on variations of the network in which the inductance (but
not the resonant frequency) of the "reflectors" was changed. First, the
series inductance was equally "apportioned" among the three "reflectors";
and, a "resonator" impedance of 240 Ohms at 5.5 Times the AC power line
frequency was employed. Next, the series inductance was "apportioned"
among the three "reflectors" in a weighted manner; and, a "resonator"
impedance of 330 Ohms at 5.5 Times the AC power line frequency was
employed. (No damping network was employed.) (Also, again, a constant, 100
watt load was employed.) It is important to note how the power factor
changes as the series inductance increases.
__________________________________________________________________________
Component Values
#1 #2 #3 #4 #5 #6 #7 #8
__________________________________________________________________________
"Reflector" (540-544-546)
Reson. Freq. 7th 7th 7th 7th 7th 7th 7th 7th
(540) in H. .0153
.0191
.0240
.0306
.0382
.0450
.0573
.0649
(546) in Mfd 9.390
7.520
5.790
4.700
3.760
3.140
2.510
2.210
(544) in Ohms 240 240 240 240 240 240 240 240
"Reflector" (550-552)
Reson. Freq. 5th 5th 5th 5th 5th 5th 5th 5th
(550) in H. .0153
.0191
.0248
.0306
.0382
.0458
.0573
.0649
(552) in Mfd 18.40
14.70
11.30
9.210
7.370
6.140
4.910
4.340
"Reflector" (650-652)
Reson. Freq. 3rd 3rd 3rd 3rd 3rd 3rd 3rd 3rd
(650) in H. .0153
.0191
.0248
.0306
.0382
.0458
.0573
.0649
(652) in Mfd 51.10
40.90
31.50
25.50
20.50
17.10
13.60
12.00
"Resonator" (670-672)
Reson. Freq. 5.5 5.5 5.5 5.5 5.5 5.5 5.5 5.5
(670) in H. .1160
.1160
.1160
.1160
.1160
.1160
.1160
.1160
(672) in Mfd 2.010
2.010
2.010
2.010
2.010
2.010
2.010
2.010
For a "Resonator" Impedance of 240 Ohms at
5.5 Times the AC Power Line Frequency
Performance Characteristics
Total Series .0459
.0573
.0744
.0918
.1146
.1374
.1719
.1947
Inductance
in Henrys
Average DC 137.5
139.0
141.5
142.5
144.5
145.0
143.5
141.5
Output Voltage
in Volts
Power Factor 0.882
0.875
0.905
0.913
0.935
0.953
0.944
0.935
Harmonic Levels
3rd 5.5% 4.0% 2.2% 1.5% 1.0% 0.6% 0.5% 0.4%
5th 0.5% 0.2% 0.2% 0.1% 0.1% 0.1% 0.2% 0.1%
7th 35.0%
30.0%
26.0%
22.0%
18.0%
15.0%
11.0%
9.8%
9th 18.0%
14.0%
11.0%
9.0% 7.2% 6.1% 4.9% 4.1%
11th 4.9% 4.0% 3.6% 2.9% 2.1% 1.6% 1.0% 0.9%
__________________________________________________________________________
______________________________________
Component
Values #1 #2 #3 #4 #5 #6
______________________________________
"Reflector"
(540-544-546)
Resonant 7th 7th 7th 7th 7th 7th
Frequency
(540) in H.
.0248 .0306 .0382 .0458 .0573 .0649
(546) in Mfd
5.790 4.700 3.760 3.140 2.510 2.210
(544) in Ohms
330 330 330 330 330 330
"Reflector"
(550-552)
Resonant 5th 5th 5th 5th 5th 5th
Frequency
(550) in H.
.0248 .0306 .0382 .0458 .0573 .0649
(552) in Mfd
11.30 9.210 7.370 6.140 4.910 4.340
"Reflector"
(650-652)
Resonant 3rd 3rd 3rd 3rd 3rd 3rd
Frequency
(650) in H.
.0248 .0360 .0382 .0458 .0573 .0649
(652) in Mfd
31.50 25.50 20.50 17.10 13.60 12.00
"Resonator"
(670-672)
Resonant 5.5 5.5 5.5 5.5 5.5 5.5
Frequency
(670) in H.
.1590 .1590 .1590 .1590 .1590 .1590
(672) in Mfd
1.460 1.460 1.460 1.460 1.460 1.460
For a "Resonator" Impedance of 330 Ohms at
5.5 Times the AC Power Line Frequency
Performance
Character-
istics
Total Series
.0744 .0918 .1146 .1374 .1719 .1947
Inductance
in Henrys
Average DC
138.5 139.0 140.5 142.5 142.5 141.5
Output
Voltage
in Volts
Power Factor
0.913 0.953 0.926 0.944 0.944 0.939
Harmonic
Levels
3rd 2.1% 2.2% 1.1% 0.9% 0.5% 0.4%
5th 0.4% 0.3% 0.1% 0.2% 0.2% 0.1%
7th 30.0% 27.0% 22.0% 18.0% 14.0% 12.0%
9th 13.0% 10.0% 8.1% 6.9% 5.4% 4.9%
11th 4.5% 4.0% 3.3% 2.7% 1.9% 1.7%
______________________________________
Again, it is important to note how the power factor changes as the series
inductance increases. This is just the opposite of the performance of the
network absent the "resonator". To illustrate the this point, the
performance computations were repeated for the network absent the
"reflector". (Again, no damping network was employed.) (Also, again, a
constant, 100 watt load was employed.) With the constant, 100 watt load
and with a total series inductance of 0.1947 henrys, the DC output voltage
collapsed.
______________________________________
Component
Values #1 #2 #3 #4 #5 #6
______________________________________
"Reflector"
(540-544-546)
Resonant 7th 7th 7th 7th 7th 7th
Frequency
(540) in H.
.0248 .0306 .0382 .0458 .0573 .0649
(546) in Mfd
5.790 4.700 3.760 3.140 2.510 2.210
(544) in Ohms
330 330 330 330 330 330
"Reflector"
(550-552)
Resonant 5th 5th 5th 5th 5th 5th
Frequency
(550) in H.
.0248 .0306 .0382 .0458 .0573 .0649
(552) in Mfd
11.30 9.210 7.370 6.140 4.910 4.340
"Reflector"
(650-652)
Resonant 3rd 3rd 3rd 3rd 3rd 3rd
Frequency
(650) in H.
.0248 .0360 .0382 .0458 .0573 .0649
(652) in Mfd
31.50 25.50 20.50 17.10 13.60 12.00
"Resonator"
(670-672)
Resonant * * * * * *
Frequency
(670) in H.
* * * * * *
(672) in Mfd
* * * * * *
Performance
Character-
istics
Total Series
.0744 .0918 .1146 .1374 .1719 .1947
Inductance
in Henrys
Average DC
131.0 129.0 126.0 121.0 101.0 *
Output
Voltage
in Volts
Power Factor
0.878 0.905 0.890 0.871 0.738 *
Harmonic
Levels
3rd 2.5% 1.6% 1.0% 0.7% 0.3 *
5th 0.4% 0.3% 0.3% 0.1% 0.1% *
7th 32.0% 28.0% 22.0% 17.0% 11.0% *
9th 9.6% 7.2% 6.0% 5.5% 4.4% *
11th 4.4% 3.0% 1.7% 1.4% 1.8% *
______________________________________
To illustrate the performance of the harmonic currents isolating network
shown in FIG. 4 as a function of the resonant frequency of the
"resonator", computations were performed on variations of the network in
which the resonant frequency of the "resonators" was changed. In all
computations, a "resonator" impedance of 330 Ohms was employed. (No
damping network was employed.) (Also, again, a constant, 100 watt load was
employed.) For "resonator" frequencies of 4.9 and 5.0, the DC output
voltage collapsed.
__________________________________________________________________________
Component Values
#1 #2 #3 #4 #5 #6 #7 #8
__________________________________________________________________________
"Reflector" (540-544-546)
Reson. Freq. 7th 7th 7th 7th 7th 7th 7th 7th
(540) in H. .0649
.0649
.0649
.0649
.0649
.0649
.0649
.0649
(546) in Mfd 2.210
2.210
2.210
2.210
2.210
2.210
2.210
2.210
(544) in Ohms 330 330 330 330 330 330 330 330
"Reflector" (550-552)
Reson. Freq. 5th 5th 5th 5th 5th 5th 5th 5th
(550) in H. .0649
.0649
.0649
.0649
.0649
.0649
.0649
.0649
(552) in Mfd 4.340
4.340
4.340
4.340
4.340
4.340
4.340
4.340
"Reflector" (650-652)
Reson. Freq. 3rd 3rd 3rd 3rd 3rd 3rd 3rd 3rd
(650) in H. .0649
.0649
.0649
.0649
.0649
.0649
.0649
.0649
(652) in Mfd 12.00
12.00
12.00
12.00
12.00
12.00
12.00
12.00
"Resonator" (670-672)
Reson. Freq. 4.9 5.0 5.3 5.4 5.5 5.75 5.95 6.05
(670) in H. .1786
.1751
.1652
.1621
.1590
.1522
.1471
.1447
(672) in Mfd 1.640
1.608
1.517
1.401
1.460
1.390
1.351
1.321
For a "Resonator" Impedance of 330 Ohms
Performance Characteristics
"Resonator" 4.90 5.00 5.30 5.40 5.50 5.75 5.95 6.05
Frequency
(Times Line F.)
Average DC * * 135.5
138.5
141.5
130.5
118.5
111.5
Output Voltage
in Volts
Power Factor * * 0.913
0.930
0.939
0.909
0.854
0.807
Harmonic Levels
3rd * * 0.3% 0.4% 0.4% 0.4% 0.3% 0.2%
5th * * 0.1% 0.1% 0.1% 0.1% 0.1% 0.1%
7th * * 11.0%
12.0%
12.0%
12.0%
11.0%
10.0%
9th * * 5.3% 5.1% 4.9% 4.6% 4.3% 4.0%
11th * * 1.7% 1.6% 1.7% 1.7% 1.7% 1.8%
__________________________________________________________________________
To illustrate how "apportioning" the series inductance among the three
"reflectors" affects the distribution of harmonic energy for the harmonic
currents isolating network shown in FIG. 4, additional computations were
performed.
______________________________________
Component
Values #1 #2 #3 #4 #5 #6
______________________________________
"Reflector"
(540-544-546)
Resonant 7th 7th 7th 7th 7th 7th
Frequency
(540) in H.
.0153 .0230 .0306 .0460 .0458 .0688
(546) in Mfd
9.390 6.270 4.700 3.135 3.140 2.090
(544) in Ohms
240 240 240 240 240 240
"Reflector"
(550-552)
Resonant 5th 5th 5th 5th 5th 5th
Frequency
(550) in H.
.0153 .00573 .0306 .0115 .0458 .0172
(552) in Mfd
18.40 49.10 9.210 24.55 6.140 16.40
"Reflector"
(650-652)
Resonant 3rd 3rd 3rd 3rd 3rd 3rd
Frequency
(650) in H.
.0153 .0172 .0306 .0344 .0458 .0516
(652) in Mfd
51.10 45.50 25.50 22.75 17.10 15.20
"Resonator"
(670-672)
Resonant 5.5 5.5 5.5 5.5 5.5 5.5
Frequency
(670) in H.
.1160 .1160 .1160 .1160 .1160 .1160
(672) in Mfd
2.010 2.010 2.010 2.010 2.010 2.010
For a "Resonator" Impedance of 240 Ohms at
5.5 Times the AC Power Line Frequency
Performance
Character-
istics
Average DC
137.5 137.5 142.5 143.5 145.0 145.0
Output
Voltage
in Volts
Power Factor
0.882 0.890 0.913 0.935 0.953 0.962
Harmonic
Levels
3rd 5.5% 5.2% 1.5% 1.4% 0.6% 0.6%
5th 0.5% 7.5% 0.1% 2.2% 0.1% 1.0%
7th 35.0% 22.0% 22.0% 13.0% 15.0% 8.5%
9th 18.0% 3.1% 9.0% 2.8% 6.1% 2.9%
11th 4.9% 1.5% 2.9% 1.4% 1.6% 0.7%
______________________________________
To illustrate the performance of the harmonic currents isolating network
shown in FIG. 4 with the addition of the "damping" network, additional
computations were performed. First, computations were performed with one
level of series inductance; then, computations were performed with a
higher level of series inductance. In each case, a slight reduction in the
level of the higher order harmonics was achieved, however, at a
considerable sacrifice in power factor. (Also, again, a constant, 100 watt
load was employed.)
______________________________________
Component Values #1 #2 #3 #4
______________________________________
"Reflector" (540-544-546)
Resonant Frequency
7th 7th 7th 7th
(540) in H. .0460 .0460 .0460 .0460
(546) in Mfd 3.135 3.135 3.135 3.135
(544) in Ohms 240 240 240 240
"Reflector" (550-552)
Resonant Frequency
5th 5th 5th 5th
(550) in H. .0115 .0115 .0115 .0115
(552) in Mfd 24.55 24.55 24.55 24.55
"Reflector" (650-652)
Resonant Frequency
3rd 3rd 3rd 3rd
(650) in H. .0344 .0344 .0344 .0344
(652) in Mfd 22.75 22.75 22.75 22.75
"Resonator" (670-672)
Resonant Frequency
5.5 5.5 5.5 5.5
(670) in H. .1160 .1160 .1160 .1160
(672) in Mfd 2.010 2.010 2.010 2.010
For a "Resonator" Impedance of 240 Ohms at
5.5 Times the AC Power Line Frequency
Performance Characteristics
Damping Component Values
Resistance none 417 O 341 O 295 O
Capacitance none 1 mfd 2 mfd 4 mfd
Average DC 144.0 146.5 147.5 149.0
Output Voltage
in Volts
Power Factor 0.935 0.930 0.905 0.841
Harmonic Levels
3rd 1.4% 1.3% 1.3% 1.1%
5th 2.2% 1.8% 1.7% 1.4%
7th 13.0% 12.0% 10.0% 8.9%
9th 2.8% 2.8% 2.6% 2.2%
11th 1.4% 1.0% 0.9% 0.8%
______________________________________
______________________________________
Component Values #1 #2 #3 #4
______________________________________
"Reflector" (540-544-546)
Resonant Frequency
7th 7th 7th 7th
(540) in H. .0688 .0688 .0688 .0688
(546) in Mfd 2.090 2.090 2.090 2.090
(544) in Ohms 240 240 240 240
"Reflector" (550-552)
Resonant Frequency
5th 5th 5th 5th
(550) in H. .0172 .0172 .0172 .0172
(552) in Mfd 16.40 16.40 16.40 16.40
"Reflector" (650-652)
Resonant Frequency
3rd 3rd 3rd 3rd
(650) in H. .0516 .0516 .0516 .0516
(652) in Mfd 15.20 15.20 15.20 15.20
"Resonator" (670-672)
Resonant Frequency
5.5 5.5 5.5 5.5
(670) in H. .1160 .1160 .1160 .1160
(672) in Mfd 2.010 2.010 2.010 2.010
For a "Resonator" Impedance of 240 Ohms at
5.5 Times the AC Power Line Frequency
Performance Characteristics
Damping Component Values
Resistance none 417 O 417 O 341 O
Capacitance none 1 mfd 1 mfd 2 mfd
Average DC 145.0 148.0 148.0 150.0
Output Voltage
in Volts
Power Factor 0.962 0.935 0.935 0.922
Harmonic Levels
3rd 0.6% 0.6% 0.6% 0.5%
5th 1.0% 0.7% 0.8% 0.7%
7th 8.5% 7.5% 7.3% 6.5%
9th 2.8% 2.8% 2.8% 2.5%
11th 0.7% 0.3% 0.3% 0.2%
______________________________________
The "resonator" impedance also influences the harmonic levels when the
"damping" network is added to the harmonic currents isolating network
shown in FIG. 4, as illustrated by the additional computations. Also,
"resonator" impedances of 165 and 240 ohms, as indicated. (Also, again, a
constant, 100 watt load was employed.)
______________________________________
Component Values #1 #2 #3
______________________________________
"Reflector" (540-544-546)
Resonant Frequency
7th 7th 7th
(540) in H. .0688 .0688 .0688
(546) in Mfd 2.090 2.090 2.090
(544) in Ohms 165 165. 240
"Reflector" (550-552)
Resonant Frequency
5th 5th 5th
(550) in H. .0172 .0172 .0172
(552) in Mfd 16.40 16.40 16.40
"Reflector" (650-652)
Resonant Frequency
3rd 3rd 3rd
(650) in H. .0516 .0516 .0516
(652) in Mfd 15.20 15.20 15.20
"Resonator" (670-672)
Resonant Frequency
5.5 5.5 5.5
(670) in H. .0795 .0795 .1160
(672) in Mfd 2.920 2.920 2.010
"Resonator" Impedance at
165 165 240
5.5 Times the AC Power
Line Frequency in Ohms
Performance Characteristics
Damping Component Values
Resistance none 230 none
Capacitance none 3.08 none
Average DC 146.0 156.0 145.0
Output Voltage
in Volts
Power Factor 0.957 0.901 0.962
Harmonic Levels
3rd 0.4% 0.4% 0.6%
5th 0.8% 0.5% 1.0%
7th 5.9% 4.6% 8.5%
9th 2.7% 2.0% 2.8%
11th 1.1% 0.4% 0.7%
______________________________________
Turning now to FIG. 5, a number of computer generated waveforms are
illustrated which are associated with the three "reflector" harmonic
currents isolating network shown in FIG. 4. For generating the waveforms,
the following component values were employed:
______________________________________
Component Values
______________________________________
"Reflector" (540-544-546)
Resonant Frequency 7th
(540) in H. .0688
(546) in Mfd 2.090
(544) in Ohms 240
"Reflector" (550-552)
Resonant Frequency 5th
(550) in H. .0172
(552) in Mfd 16.40
"Reflector" (650-652)
Resonant Frequency 3rd
(650) in H. .0516
(652) in Mfd 15.20
"Resonator" (670-672)
Resonant Frequency 5.5
(670) in H. .1160
(672) in Mfd 2.010
For a "Resonator" Impedance
of 240 Ohms at 5.5 Times the
AC Power Line Frequency
Damping Component Values
none
______________________________________
Specifically, at the top of the figure, generally designated by the number
710, is the (sinusoidal) waveform associated with the AC power line
potential developed on AC power line 512. Below AC power line potential
waveform 710, generally designated 720, is the near trapezoidal
(squarewave) waveform of the potential developed across the input
(522-522') of the bridge rectifier (680) of the DC power supply (514).
Next, below the waveform (720) of the potential developed across the input
(522-522') of the bridge rectifier (680) of the DC power supply (514) is
the waveform, designated 730, of the current therethrough. It is important
to note the sinusoidal component of the waveform at the "resonator"
frequency. Finally, below the waveform (730) of the current through the
input (522-522') of the DC power supply (514) is the waveform, designated
740, of the current through the "resonator" (inductor 670 and capacitor
672). Again, it is important to note the sinusoidal component of the
waveform at the "resonator" frequency.
It is important to note that in each of the above embodiments of the
present invention, since the components employed are all passive, they may
be scaled up or down. First, the ratio of the desired power rating to the
given power rating is obtained. Then, the inductance of each of the
inductors is divided by the ratio; the capacitance of each of the
capacitors is multiplied by the ratio; and, the resistance of each of the
resistors is divided by the ratio.
It is contemplated that after having read the preceding disclosure, certain
alterations and modifications of the present invention will no doubt
become apparent to those skilled in the art. It is therefore intended that
the following claims be interpreted to cover all such alterations and
modifications as fall within the true spirit and scope of the invention.
Top